LMC6492, LMC6494
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SNOS724D – AUGUST 2000 – REVISED MARCH 2013
LMC6492 Dual/LMC6494 Quad CMOS Rail-to-Rail Input and Output Operational Amplifier
Check for Samples: LMC6492, LMC6494
FEATURES
1
(Typical Unless Otherwise Noted)
2
•
•
•
•
•
•
•
•
Rail-to-Rail Input Common-Mode Voltage
Range, Ensured Over Temperature
Rail-to-Rail Output Swing within 20 mV of
Supply Rail, 100 kΩ Load
Operates from 5V to 15V Supply
Excellent CMRR and PSRR 82 dB
Ultra Low Input Current 150 fA
High Voltage Gain (RL = 100 kΩ) 120 dB
Low Supply Current (@ VS = 5V) 500
μA/Amplifier
Low Offset Voltage Drift 1.0 μV/°C
APPLICATIONS
•
•
•
•
•
Automotive Transducer Amplifier
Pressure Sensor
Oxygen Sensor
Temperature Sensor
Speed Sensor
DESCRIPTION
The LMC6492/LMC6494 amplifiers were specifically
developed for single supply applications that operate
from −40°C to +125°C. This feature is well-suited for
automotive systems because of the wide temperature
range. A unique design topology enables the
LMC6492/LMC6494 common-mode voltage range to
accommodate input signals beyond the rails. This
eliminates non-linear output errors due to input
signals exceeding a traditionally limited commonmode voltage range. The LMC6492/LMC6494 signal
range has a high CMRR of 82 dB for excellent
accuracy in non-inverting circuit configurations.
The
LMC6492/LMC6494
rail-to-rail
input
is
complemented by rail-to-rail output swing. This
assures maximum dynamic signal range which is
particularly important in 5V systems.
Ultra-low input current of 150 fA and 120 dB open
loop gain provide high accuracy and direct interfacing
with high impedance sources.
Connection Diagram
Figure 1. 8-Pin PDIP/SOIC - Top View
Figure 2. 14-Pin PDIP/SOIC - Top View
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2000–2013, Texas Instruments Incorporated
LMC6492, LMC6494
SNOS724D – AUGUST 2000 – REVISED MARCH 2013
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These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Absolute Maximum Ratings (1) (2)
ESD Tolerance (3)
2000V
Differential Input Voltage
±Supply Voltage
(V+) + 0.3V, (V−) − 0.3V
Voltage at Input/Output Pin
−
+
Supply Voltage (V − V )
16V
Current at Input Pin
±5 mA
Current at Output Pin (4)
±30 mA
Current at Power Supply Pin
40 mA
Lead Temp. (Soldering, 10 sec.)
260°C
−65°C to +150°C
Storage Temperature Range
Junction Temperature (5)
(1)
(2)
(3)
(4)
(5)
150°C
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications and the test
conditions, see the Electrical Characteristics.
If Military/Aerospace specified devices are required, please contact the TI Sales Office/ Distributors for availability and specifications.
Human body model, 1.5 kΩ in series with 100 pF.
Applies to both single-supply and split-supply operation. Continuous short operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature at 150°C. Output currents in excess of ±30 mA over long term may adversely
affect reliability.
The maximum power dissipation is a function of TJ(max), θJA and TA. The maximum allowable power dissipation at any ambient
temperature is PD = (TJ(max) − TA)/θJA. All numbers apply for packages soldered directly into a PC board.
Operating Conditions (1)
2.5V ≤ V+ ≤ 15.5V
Supply Voltage
Junction Temperature Range
Thermal Resistance (θJA)
(1)
LMC6492AE, LMC6492BE
−40°C ≤ TJ ≤ +125°C
LMC6494AE, LMC6494BE
−40°C ≤ TJ ≤ +125°C
P Package, 8-Pin PDIP
108°C/W
D Package, 8-Pin SOIC
171°C/W
P Package, 14-Pin PDIP
78°C/W
D Package, 14-Pin SOIC
118°C/W
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications and the test
conditions, see the Electrical Characteristics.
DC Electrical Characteristics
Unless otherwise specified, all limits specified for TJ = 25°C, V+ = 5V, V− = 0V, VCM = VO = V+/2 and RL > 1 MΩ. Boldface
limits apply at the temperature extremes
Symbol
VOS
Parameter
Conditions
Input Offset Voltage
TCVOS
Typ (1)
0.11
Input Offset Voltage
LMC6492AE
LMC6492BE
LMC6494AE
LMC6494BE
Limit (2)
Limit (2)
3.0
6.0
mV
3.8
6.8
max
Units
μV/°C
1.0
Average Drift
IB
Input Bias Current
See (3)
0.15
200
200
pA max
IOS
Input Offset Current
See (3)
0.075
100
100
pA max
RIN
Input Resistance
(1)
(2)
(3)
2
Tera Ω
>10
Typical Values represent the most likely parametric norm.
All limits are specified by testing or statistical analysis.
Specified limits are dictated by tester limits and not device performance. Actual performance is reflected in the typical value.
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DC Electrical Characteristics (continued)
Unless otherwise specified, all limits specified for TJ = 25°C, V+ = 5V, V− = 0V, VCM = VO = V+/2 and RL > 1 MΩ. Boldface
limits apply at the temperature extremes
Symbol
Parameter
Typ (1)
Conditions
LMC6492AE
LMC6492BE
LMC6494AE
LMC6494BE
Limit
CIN
Common-Mode
(2)
Limit
Units
(2)
3
pF
Input Capacitance
CMRR
Common-Mode
Rejection Ratio
0V ≤ VCM ≤ 15V
82
−PSRR
VCM
63
60
58
65
63
60
58
65
63
dB
60
58
min
82
65
63
dB
60
58
min
V− −0.3
−0.25
−0.25
V
0
0
max
V+ + 0.25
V+ + 0.25
V
V = 15V
0V ≤ VCM ≤ 5V
+PSRR
65
+
82
+
Positive Power Supply
5V ≤ V ≤ 15V,
Rejection Ratio
VO = 2.5V
Negative Power Supply
0V ≤ V− ≤ −10V,
Rejection Ratio
VO = 2.5V
Input Common-Mode
V+ = 5V and 15V
Voltage Range
For CMRR ≥ 50 dB
82
V+ + 0.3
+
V
AV
VO
Large Signal Voltage Gain
Output Swing
RL = 2 kΩ: (4)
+
V = 5V
Sinking
40
min
4.7
RL = 600Ω to V+/2
0.3
14.7
RL = 2 kΩ to V+/2
0.16
14.1
+
RL = 600Ω to V /2
0.5
ISC
ISC
(4)
(5)
min
V/mV
0.1
V+ = 15V
V
300
4.9
V+ = 15V
+
Sourcing
RL = 2 kΩ to V+/2
V+ = 5V
dB
min
Output Short Circuit Current
Sourcing, VO = 0V
25
V+ = 5V
Sinking, VO = 5V
22
Output Short Circuit Current
Sourcing, VO = 0V
30
V+ = 15V
Sinking, VO = 5V (5)
30
4.8
4.8
V
4.7
4.7
min
0.18
0.18
V
0.24
0.24
max
4.5
4.5
V
4.24
4.24
min
0.5
0.5
V
0.65
0.65
max
14.4
14.4
V
14.0
14.0
min
0.35
0.35
V
0.5
0.5
max
13.4
13.4
V
13.0
13.0
min
1.0
1.0
V
1.5
1.5
max
16
16
10
10
11
11
8
8
28
28
20
20
30
30
22
22
mA
min
V+ = 15V, VCM = 7.5V and RL connected to 7.5V. For Sourcing tests, 7.5V ≤ VO ≤ 11.5V. For Sinking tests, 3.5V ≤ VO ≤ 7.5V.
Do not short circuit output to V+, when V+ is greater than 13V or reliability will be adversely affected.
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DC Electrical Characteristics (continued)
Unless otherwise specified, all limits specified for TJ = 25°C, V+ = 5V, V− = 0V, VCM = VO = V+/2 and RL > 1 MΩ. Boldface
limits apply at the temperature extremes
Symbol
Parameter
Typ (1)
Conditions
LMC6492AE
LMC6492BE
LMC6494AE
LMC6494BE
Limit
IS
Supply Current
LMC6492
1.0
V+ = +5V, VO = V+/2
LMC6492
+
1.3
+
V = +15V, VO = V /2
LMC6494
2.0
V+ = +5V, VO = V+/2
LMC6494
2.6
V+ = +15V, VO = V+/2
(2)
Limit
Units
(2)
1.75
1.75
mA
2.1
2.1
max
1.95
1.95
mA
2.3
2.3
max
3.5
3.5
mA
4.2
4.2
max
3.9
3.9
mA
4.6
4.6
max
AC Electrical Characteristics
Unless otherwise specified, all limits specified for TJ = 25°C, V+ = 5V, V− = 0V, VCM = VO = V+/2 and RL > 1 MΩ. Boldface
limits apply at the temperature extremes
Symbol
Parameter
Conditions
Typ
(1)
LMC6492AE
LMC6492BE
LMC6494AE
LMC6494BE
Limit (2)
Limit (2)
0.7
0.7
0.5
0.5
Units
SR
Slew Rate
See (3)
1.3
GBW
Gain-Bandwidth Product
V+ = 15V
1.5
MHz
φm
Phase Margin
50
Deg
Gm
Gain Margin
15
dB
Amp-to-Amp Isolation
See
(4)
150
dB
Input-Referred
F = 1 kHz
37
Voltage Noise
VCM = 1V
Input-Referred
F = 1 kHz
0.06
F = 1 kHz, AV = −2
0.01
en
in
nV/√HZ
pA/√HZ
Current Noise
T.H.D.
Total Harmonic Distortion
Vμs min
RL = 10 kΩ, VO = −4.1 VPP
F = 10 kHz, AV = −2
RL = 10 kΩ, VO = 8.5 VPP
%
0.01
V+ = 10V
(1)
(2)
(3)
(4)
4
Typical Values represent the most likely parametric norm.
All limits are specified by testing or statistical analysis.
V+ = 15V. Connected as voltage follower with 10V step input. Number specified is the slower of the positive and negative slew rates.
Input referred, V+ = 15V and RL = 100 kΩ connected to 7.5V. Each amp excited in turn with 1 kHz to produce VO = 12 VPP.
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Typical Performance Characteristics
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
Supply Current vs
Supply Voltage
Input Current vs
Temperature
Figure 3.
Figure 4.
Sourcing Current vs
Output Voltage
Sourcing Current vs
Output Voltage
Figure 5.
Figure 6.
Sourcing Current vs
Output Voltage
Sinking Current vs
Output Voltage
Figure 7.
Figure 8.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
6
Sinking Current vs
Output Voltage
Sinking Current vs
Output Voltage
Figure 9.
Figure 10.
Output Voltage Swing vs
Supply Voltage
Input Voltage Noise
vs Frequency
Figure 11.
Figure 12.
Input Voltage Noise
vs Input Voltage
Input Voltage Noise
vs Input Voltage
Figure 13.
Figure 14.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
Input Voltage Noise
vs Input Voltage
Crosstalk Rejection
vs Frequency
Figure 15.
Figure 16.
Crosstalk Rejection
vs Frequency
Positive PSRR
vs Frequency
Figure 17.
Figure 18.
Negative PSRR
vs Frequency
CMRR vs
Frequency
Figure 19.
Figure 20.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
8
CMRR vs
Input Voltage
CMRR vs
Input Voltage
Figure 21.
Figure 22.
CMRR vs
Input Voltage
ΔVOS
vs CMR
Figure 23.
Figure 24.
ΔVOS
vs CMR
Input Voltage vs
Output Voltage
Figure 25.
Figure 26.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
Input Voltage vs
Output Voltage
Open Loop
Frequency Response
Figure 27.
Figure 28.
Open Loop
Frequency Response
Open Loop Frequency Response
vs Temperature
Figure 29.
Figure 30.
Maximum Output Swing
vs Frequency
Gain and Phase vs
Capacitive Load
Figure 31.
Figure 32.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
10
Gain and Phase vs
Capacitive Load
Open Loop Output Impedance
vs Frequency
Figure 33.
Figure 34.
Open Loop Output Impedance
vs Frequency
Slew Rate vs
Supply Voltage
Figure 35.
Figure 36.
Non-Inverting Large
Signal Pulse Response
Non-Inverting Large
Signal Pulse Response
Figure 37.
Figure 38.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
Non-Inverting Large
Signal Pulse Response
Non-Inverting Small
Signal Pulse Response
Figure 39.
Figure 40.
Non-Inverting Small
Signal Pulse Response
Non-Inverting Small
Signal Pulse Response
Figure 41.
Figure 42.
Inverting Large
Signal Pulse Response
Inverting Large Signal
Pulse Response
Figure 43.
Figure 44.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
12
Inverting Large Signal
Pulse Response
Inverting Small Signal
Pulse Response
Figure 45.
Figure 46.
Inverting Small Signal
Pulse Response
Inverting Small Signal
Pulse Response
Figure 47.
Figure 48.
Stability vs
Capacitive Load
Stability vs
Capacitive Load
Figure 49.
Figure 50.
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Typical Performance Characteristics (continued)
VS = +15V, Single Supply, TA = 25°C unless otherwise specified
Stability vs
Capacitive Load
Stability vs
Capacitive Load
Figure 51.
Figure 52.
Stability vs
Capacitive Load
Stability vs
Capacitive Load
Figure 53.
Figure 54.
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APPLICATION HINTS
INPUT COMMON-MODE VOLTAGE RANGE
Unlike Bi-FET amplifier designs, the LMC6492/4 does not exhibit phase inversion when an input voltage exceeds
the negative supply voltage. Figure 55 shows an input voltage exceeding both supplies with no resulting phase
inversion on the output.
Figure 55. An Input Voltage Signal Exceeds the
LMC6492/4 Power Supply Voltages with
No Output Phase Inversion
The absolute maximum input voltage is 300 mV beyond either supply rail at room temperature. Voltages greatly
exceeding this absolute maximum rating, as in Figure 56, can cause excessive current to flow in or out of the
input pins possibly affecting reliability.
Figure 56. A ±7.5V Input Signal Greatly
Exceeds the 5V Supply in Figure 57 Causing
No Phase Inversion Due to RI
14
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Applications that exceed this rating must externally limit the maximum input current to ±5 mA with an input
resistor (RI) as shown in Figure 57.
Figure 57. RI Input Current Protection for
Voltages Exceeding the Supply Voltages
RAIL-TO-RAIL OUTPUT
The approximate output resistance of the LMC6492/4 is 110Ω sourcing and 80Ω sinking at Vs = 5V. Using the
calculated output resistance, maximum output voltage swing can be esitmated as a function of load.
COMPENSATING FOR INPUT CAPACITANCE
It is quite common to use large values of feedback resistance for amplifiers with ultra-low input current, like the
LMC6492/4.
Although the LMC6492/4 is highly stable over a wide range of operating conditions, certain precautions must be
met to achieve the desired pulse response when a large feedback resistor is used. Large feedback resistors with
even small values of input capacitance, due to transducers, photodiodes, and circuit board parasitics, reduce
phase margins.
When high input impedances are demanded, guarding of the LMC6492/4 is suggested. Guarding input lines will
not only reduce leakage, but lowers stray input capacitance as well. (See Printed-Circuit-Board Layout for High
Impedance Work).
The effect of input capacitance can be compensated for by adding a capacitor, Cf, around the feedback resistors
(as in Figure 55 ) such that:
(1)
or
R1 CIN ≤ R2 Cf
(2)
Since it is often difficult to know the exact value of CIN, Cf can be experimentally adjusted so that the desired
pulse response is achieved. Refer to the LMC660 and LMC662 for a more detailed discussion on compensating
for input capacitance.
Figure 58. Cancelling the Effect of Input Capacitance
CAPACITIVE LOAD TOLERANCE
All rail-to-rail output swing operational amplifiers have voltage gain in the output stage. A compensation capacitor
is normally included in this integrator stage. The frequency location of the dominant pole is affected by the
resistive load on the amplifier. Capacitive load driving capability can be optimized by using an appropriate
resistive load in parallel with the capacitive load (see Typical Curves).
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Direct capacitive loading will reduce the phase margin of many op-amps. A pole in the feedback loop is created
by the combination of the op-amp's output impedance and the capacitive load. This pole induces phase lag at the
unity-gain crossover frequency of the amplifier resulting in either an oscillatory or underdamped pulse response.
With a few external components, op amps can easily indirectly drive capacitive loads, as shown in Figure 59.
Figure 59. LMC6492/4 Noninverting Amplifier, Compensated to Handle Capacitive Loads
PRINTED-CIRCUIT-BOARD LAYOUT FOR HIGH-IMPEDANCE WORK
It is generally recognized that any circuit which must operate with less than 1000 pA of leakage current requires
special layout of the PC board. When one wishes to take advantage of the ultra-low bias current of the
LMC6492/4, typically 150 fA, it is essential to have an excellent layout. Fortunately, the techniques of obtaining
low leakages are quite simple. First, the user must not ignore the surface leakage of the PC board, even though
it may sometimes appear acceptably low, because under conditions of high humidity or dust or contamination,
the surface leakage will be appreciable.
To minimize the effect of any surface leakage, lay out a ring of foil completely surrounding the LMC6492/4's
inputs and the terminals of components connected to the op-amp's inputs, as in Figure 60. To have a significant
effect, guard rings should be placed on both the top and bottom of the PC board. This PC foil must then be
connected to a voltage which is at the same voltage as the amplifier inputs, since no leakage current can flow
between two points at the same potential. For example, a PC board trace-to-pad resistance of 1012Ω, which is
normally considered a very large resistance, could leak 5 pA if the trace were a 5V bus adjacent to the pad of the
input.
This would cause a 33 times degradation from the LMC6492/4's actual performance. If a guard ring is used and
held within 5 mV of the inputs, then the same resistance of 1011Ω will only cause 0.05 pA of leakage current. See
Figure 61 for typical connections of guard rings for standard op-amp configurations.
Figure 60. Examples of Guard Ring in PC Board Layout
16
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Inverting Amplifier
Non-Inverting Amplifier
Follower
Figure 61. Typical Connections of Guard Rings
The designer should be aware that when it is inappropriate to lay out a PC board for the sake of just a few
circuits, there is another technique which is even better than a guard ring on a PC board: Don't insert the
amplifier's input pin into the board at all, but bend it up in the air and use only air as an insulator. Air is an
excellent insulator. In this case you may have to forego some of the advantages of PC board construction, but
the advantages are sometimes well worth the effort of using point-to-point up-in-the-air wiring. See Figure 62.
(Input pins are lifted out of PC board and soldered directly to components. All other pins connected to PC board).
Figure 62. Air Wiring
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Application Circuits
Where: V0 = V1 + V2 − V3 – V4
(V1 + V2 ≥ (V3 + V4) to keep V0 > 0VDC
Figure 63. DC Summing Amplifier (VIN ≥ 0VDC and VO ≥ VDC
For
(CMRR depends on this resistor ratio match)
As shown: VO = 2(V2 − V1)
Figure 64. High Input Z, DC Differential Amplifier
Figure 65. Photo Voltaic-Cell Amplifier
18
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If R1 = R5, R3 = R6, and R4 = R7; then
∴AV ≈ 100 for circuit shown (R2 = 9.3k).
Figure 66. Instrumentation Amplifier
Figure 67. Rail-to-Rail Single Supply Low Pass Filter
This low-pass filter circuit can be used as an anti-aliasing filter with the same supply as the A/D converter. Filter
designs can also take advantage of the LMC6492/4 ultra-low input current. The ultra-low input current yields
negligible offset error even when large value resistors are used. This in turn allows the use of smaller valued
capacitors which take less board space and cost less.
Figure 68. Low Voltage Peak Detector with Rail-to-Rail Peak Capture Range
Dielectric absorption and leakage is minimized by using a polystyrene or polypropylene hold capacitor. The
droop rate is primarily determined by the value of CH and diode leakage current. Select low-leakage current
diodes to minimize drooping.
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Rf = Rx
Rf >> R1, R2, R3, and R4
Figure 69. Pressure Sensor
In a manifold absolute pressure sensor application, a strain gauge is mounted on the intake manifold in the
engine unit. Manifold pressure causes the sensing resistors, R1, R2, R3 and R4 to change. The resistors change
in a way such that R2 and R4 increase by the same amount R1 and R3 decrease. This causes a differential
voltage between the input of the amplifier. The gain of the amplifier is adjusted by Rf.
Spice Macromodel
A
•
•
•
•
•
spice macromodel is available for the LMC6492/4. This model includes accurate simulation of:
Input common-model voltage range
Frequency and transient response
GBW dependence on loading conditions
Quiescent and dynamic supply current
Output swing dependence on loading conditions
and many other characteristics as listed on the macromodel disk.
Contact your local Texas Instruments sales office to obtain an operational amplifier spice model library disk.
20
Submit Documentation Feedback
Copyright © 2000–2013, Texas Instruments Incorporated
Product Folder Links: LMC6492 LMC6494
LMC6492, LMC6494
www.ti.com
SNOS724D – AUGUST 2000 – REVISED MARCH 2013
REVISION HISTORY
Changes from Revision C (March 2013) to Revision D
•
Page
Changed layout of National Data Sheet to TI format .......................................................................................................... 20
Copyright © 2000–2013, Texas Instruments Incorporated
Product Folder Links: LMC6492 LMC6494
Submit Documentation Feedback
21
PACKAGE OPTION ADDENDUM
www.ti.com
6-Sep-2022
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
Samples
(4/5)
(6)
LMC6492AEM
NRND
SOIC
D
8
95
Non-RoHS
& Green
Call TI
Level-1-235C-UNLIM
-40 to 125
LMC64
92AEM
LMC6492AEM/NOPB
ACTIVE
SOIC
D
8
95
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC64
92AEM
Samples
LMC6492AEMX/NOPB
ACTIVE
SOIC
D
8
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC64
92AEM
Samples
LMC6492BEM/NOPB
ACTIVE
SOIC
D
8
95
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC64
92BEM
Samples
LMC6492BEMX/NOPB
ACTIVE
SOIC
D
8
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC64
92BEM
Samples
LMC6494AEM
NRND
SOIC
D
14
55
Non-RoHS
& Green
Call TI
Level-1-235C-UNLIM
-40 to 125
LMC6494
AEM
LMC6494AEM/NOPB
ACTIVE
SOIC
D
14
55
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC6494
AEM
Samples
LMC6494AEMX/NOPB
ACTIVE
SOIC
D
14
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC6494
AEM
Samples
LMC6494BEM/NOPB
ACTIVE
SOIC
D
14
55
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC6494
BEM
Samples
LMC6494BEMX/NOPB
ACTIVE
SOIC
D
14
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMC6494
BEM
Samples
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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