OPA379
OPA2379
OPA4379
SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
1.8V, 2.9µA, 90kHz, Rail-to-Rail I/O
OPERATIONAL AMPLIFIERS
FEATURES
D
D
D
D
DESCRIPTION
LOW NOISE: 2.8µVPP
The OPA379 family of micropower, low-voltage
operational amplifiers is designed for battery-powered
applications. These amplifiers operate on a supply voltage
as low as 1.8V. High-performance, single-supply
operation with rail-to-rail capability makes the OPA379
family useful for a wide range of applications.
microPower: 5.5µA (max)
LOW OFFSET VOLTAGE: 1.5mV (max)
DC PRECISION:
− CMRR: 100dB
− PSRR: 2µV/V
− AOL: 120dB
D WIDE SUPPLY VOLTAGE RANGE: 1.8V to 5.5V
D microSize PACKAGES
The OPA379 (single) is available in SC70-5, SOT23-5,
and SO-8 packages. The OPA2379 (dual) comes in
SOT23-8 and SO-8 packages. The OPA4379 (quad) is
offered in a TSSOP-14 package. All versions are specified
from −40°C to +125°C.
APPLICATIONS
D
D
D
D
In addition to microSize packages, the OPA379 family of
op amps features impressive bandwidth (90kHz), low bias
current (25pA), and low noise (80nV/√Hz) relative to the
very low quiescent current (5.5µA max).
BATTERY-POWERED INSTRUMENTS
PORTABLE DEVICES
MEDICAL INSTRUMENTS
OPAx379 RELATED PRODUCTS
HANDHELD TEST EQUIPMENT
FEATURES
PRODUCT
1µA, 70kHz, 2mV VOS, 1.8V to 5.5V Supply
OPAx349
1µA, 5.5kHz, 390µV VOS, 2.5V to 16V Supply
TLV240x
1µA, 5.5kHz, 0.6mV VOS, 2.5V to 12V Supply
TLV224x
7µA, 160kHz, 0.5mV VOS, 2.7V to 16V Supply
TLV27Lx
7µA, 160kHz, 0.5mV VOS, 2.7V to 16V Supply
TLV238x
20µA, 350kHz, 2mV VOS, 2.3V to 5.5V Supply
OPAx347
20µA, 500kHz, 550µV VOS, 1.8V to 3.6V Supply
TLV276x
45µA, 1MHz, 1mV VOS, 2.1V to 5.5V Supply
OPAx348
VCC
1/2
OPA2379
C2
C1
C
RF
REF
S
W
VCC
RB
RL
1/2
OPA2379
R1
VOUT
R1
OPA2379 in Portable Gas Meter Application
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments
semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
Copyright 2005−2006, Texas Instruments Incorporated
! !
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SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
ABSOLUTE MAXIMUM RATINGS(1)
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +7V
Signal Input Terminals, Voltage(2) . . . . . . . . . −0.5V to (V+) + 0.5V
Current(2) . . . . . . . . . . . . . . . . . . . . ±10mA
Output Short-Circuit(3) . . . . . . . . . . . . . . . . . . . . . . . . . . Continuous
Operating Temperature . . . . . . . . . . . . . . . . . . . . . −40°C to +125°C
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . −65°C to +150°C
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150°C
ESD Rating
This integrated circuit can be damaged by ESD. Texas
Instruments recommends that all integrated circuits be
handled with appropriate precautions. Failure to observe
proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to
complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could
cause the device not to meet its published specifications.
ORDERING INFORMATION(1)
Human Body Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2000V
Charged Device Model . . . . . . . . . . . . . . . . . . . . . . . . . . . 1000V
PACKAGE-LEAD
PACKAGE
DESIGNATOR
OPA379
SC70−5
DCK
AYR
OPA379
SOT23−5
DBV
AYQ
OPA379A
PRODUCT
(1) Stresses above these ratings may cause permanent damage.
Exposure to absolute maximum conditions for extended periods
may degrade device reliability. These are stress ratings only, and
functional operation of the device at these or any other conditions
beyond those specified is not supported.
(2) Input terminals are diode-clamped to the power-supply rails.
Input signals that can swing more than 0.5V beyond the supply
rails should be current-limited to 10mA or less.
(3) Short-circuit to ground, one amplifier per package.
PACKAGE
MARKING
OPA379
SO−8
D
OPA2379(2)
SOT23−8
DCN
B61
OPA2379
SO−8
D
OPA2379A
OPA4379
TSSOP−14
PW
OPA4379A
(1) For the most current package and ordering information, see the
Package Option Addendum at the end of this document, or see
the TI web site at www.ti.com.
(2) Available Q4, 2006.
PIN CONFIGURATIONS
+IN
1
V−
2
−IN
OPA379
OPA379
OPA379
5
V+
4
OUT
OUT 1
5
V+
V− 2
3
+IN 3
SC70−5
4
−IN
NC(1) 1
8
NC(1)
−IN 2
7
V+
+IN 3
6
OUT
V− 4
5
NC(1)
SOT23−5
SO−8
OUT A
1
14
OUT D
OUT B
−IN A
2
13
−IN D
6
−IN B
+IN A
3
12
+IN D
5
+IN B
V+
4
11
V−
+IN B
5
10
+IN C
−IN B
6
9
−IN C
NOTES:
OUT B 7
(1) NC denotes no internal connection.
(2) Pin 1 of the SOT23−8 package is determined by orienting the package marking as shown.
(3) Available Q4, 2006.
8
OUT C
1
8
V+
−IN
2
7
+IN
3
V−
4
B61
OUT A
OUT A 1
8
V+
OUT B
−IN A 2
7
6
−IN B
+IN A 3
5
+IN B
V− 4
SOT23−8(2)(3)
2
OPA4379
OPA2379
OPA2379
SO−8
TSSOP−14
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SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
ELECTRICAL CHARACTERISTICS: VS = +1.8V TO +5.5V
Boldface limits apply over the specified temperature range indicated.
At TA = +25°C, RL = 25kΩ connected to VS/2, and VCM < (V+) − 1V, unless otherwise noted.
OPA379, OPA2379, OPA4379
PARAMETER
OFFSET VOLTAGE
Initial Offset Voltage
Over −40°C to +125°C
Drift, −40°C to +85°C
−40°C to +125°C
vs Power Supply
Over −40°C to +125°C
INPUT VOLTAGE RANGE
Common-Mode Voltage Range
Common-Mode Rejection Ratio(1)
Over −40°C to +85°C
CONDITIONS
VOS
VS = 5V
dVOS/dT
VCM
CMRR
IB
IOS
OPEN-LOOP GAIN
Open-Loop Voltage Gain
Over −40°C to +125°C
Over −40°C to +125°C
OUTPUT
Voltage Output Swing from Rail
Over −40°C to +125°C
Over −40°C to +125°C
Short-Circuit Current
Capacitive Load Drive
Closed-Loop Output Impedance
Open-Loop Output Impedance
FREQUENCY RESPONSE
Gain Bandwidth Product
Slew Rate
Overload Recovery Time
Turn-On Time
POWER SUPPLY
Specified/Operating Voltage Range
Quiescent Current per Amplifier
Over −40°C to +125°C
TEMPERATURE
Specified/Operating Range
Storage Range
Thermal Resistance
SC70−5
SOT23−5
SOT23−8, TSSOP−14, SO−8
RO
0.4
1.5
2
mV
mV
µV/°C
µV/°C
µV/V
µV/V
10
20
V
dB
dB
(V−) < VCM < (V+) − 1V
62
dB
±5
±5
VS = 5V, VCM < = VS/2
VS = 5V
VS = 5V, RL = 25kΩ, 100mV < VO < (V+) − 100mV
VS = 5V, RL = 25kΩ, 100mV < VO < (V+) − 100mV
VS = 5V, RL = 5kΩ, 500mV < VO < (V+) − 500mV
VS = 5V, RL = 5kΩ, 500mV < VO < (V+) − 500mV
100
80
100
80
RL = 25kΩ
RL = 25kΩ
RL = 5kΩ
RL = 5kΩ
ISC
CLOAD
ROUT
UNIT
(V−) − 0.1 to (V+) + 0.1
90
100
80
en
in
AOL
MAX
(V−) < VCM < (V+) − 1V
(V−) < VCM < (V+) − 1V
INPUT IMPEDANCE
Differential
Common-Mode
NOISE
Input Voltage Noise, f = 0.1Hz to 10Hz
Input Voltage Noise Density, f = 1kHz
Input Current Noise Density, f = 1kHz
TYP
1.5
2.7
2
PSRR
Over −40°C to +125°C
INPUT BIAS CURRENT
Input Bias Current
Input Offset Current
MIN
±50
±50
pA
pA
1013 || 3
1013 || 6
Ω || pF
Ω || pF
2.8
80
1
µVPP
nV/√Hz
fA/√Hz
120
dB
dB
dB
dB
120
5
25
10
15
50
75
mV
mV
mV
mV
mA
G = 1, f = 1kHz, IO = 0
±5
See Typical Characteristics Curve
10
f = 100kHz, IO = 0
28
kΩ
90
0.03
25
1
kHz
V/µs
µs
ms
Ω
CLOAD = 30pF
GBW
SR
G = +1
VIN S GAIN > VS
tON
VS
IQ
1.8
VS = 5.5V, IO = 0
2.9
−40
−65
5.5
5.5
10
V
µA
µA
+125
+150
°C
°C
qJA
250
200
150
°C/W
°C/W
°C/W
(1) See Typical Characteristic, Common-Mode Rejection Ratio vs Frequency.
3
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SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
TYPICAL CHARACTERISTICS
At TA = +25°C, VS = 5V, RL = 25kΩ connected to VS/2, unless otherwise noted.
COMMON−MODE AND
POWER SUPPLY REJECTION RATIO
vs FREQUENCY
0
120
100
−30
100
80
−60
60
−90
40
−120
20
−150
20
−180
100k
0
0
0.1
1
10
100
1k
10k
CMRR and PSRR (dB)
120
Phase (_)
Gain (dB)
OPEN−LOOP GAIN AND PHASE
vs FREQUENCY
−PSRR
80
+PSRR
60
40
CMRR
0.1
1
10
Frequency (Hz)
MAXIMUM OUTPUT VOLTAGE
vs FREQUENCY
100
1k
Frequency (Hz)
10k
100k
QUIESCENT CURRENT
vs SUPPLY VOLTAGE
3.5
5.0
4.5
Quiescent Current (µA)
Output Voltage (VPP)
4.0
3.5
3.0
2.5
2.0
1.5
1.0
3.0
2.5
2.0
0.5
1.5
0
1k
10k
100k
1.5
2.0
2.5
3.5
4.0
4.5
Supply Voltage (V)
OUTPUT VOLTAGE
vs OUTPUT CURRENT
SHORT−CIRCUIT CURRENT
vs SUPPLY VOLTAGE
2.5
5.0
5.5
5.0
5.5
25
1.5
VS = ±2.5V
1.0
0.5
+125_ C
0
+85_C
−40_ C
+25_ C
−0.5
−1.0
−1.5
Short−Circuit Current (mA)
2.0
VOUT (V)
3.0
Frequency (Hz)
+ISC
20
−ISC
15
10
−2.0
−2.5
5
0
1
2
3
4
5
IOUT (mA)
4
6
7
8
9
10
1.5
2.0
2.5
3.0
3.5
4.0
Supply Voltage (V)
4.5
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SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
TYPICAL CHARACTERISTICS (continued)
At TA = +25°C, VS = 5V, RL = 25kΩ connected to VS/2, unless otherwise noted.
OFFSET VOLTAGE vs COMMON−MODE VOLTAGE
vs TEMPERATURE
OFFSET VOLTAGE
PRODUCTION DISTRIBUTION
15000
Unit 1
CMRR Specified Range
Population
7500
5000
2500
0
−2500
−5000
−40_C
+85_ C
+125_C
0
1
Unit 2
2
3
4
5
−1500
−1350
−1200
−1050
−900
−750
−600
−450
−300
−150
0
150
300
450
600
750
900
1050
1200
1350
1500
−15000
−0.1
−12500
5.1
−7500
−10000
Common−Mode Voltage (V)
Offset Voltage (µV)
Population
OFFSET VOLTAGE DRIFT DISTRIBUTION
(−40_C to +125_ C)
Population
OFFSET VOLTAGE DRIFT DISTRIBUTION
(−40_C to +85_ C)
≤1
≤2
≤3
≤4
≤5
≤1
>5
≤2
≤3
≤4
≤5
Offset Voltage Drift (µV/_C)
Offset Voltage Drift (µV/_C)
QUIESCENT CURRENT
vs TEMPERATURE
QUIESCENT CURRENT
PRODUCTION DISTRIBUTION
>5
5.0
4.5
4.0
Population
3.5
3.0
2.5
2.0
1.5
1.0
−50
−25
0
25
50
Temperature (_C)
75
100
125
1.00
1.20
1.40
1.60
1.80
2.00
2.20
2.40
2.60
2.80
3.00
3.20
3.40
3.60
3.80
4.00
4.20
4.40
4.60
4.80
5.00
IQ (µA)
Offset Voltage (µV)
12500
10000
Quiescent Current (µA)
5
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SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
TYPICAL CHARACTERISTICS (continued)
At TA = +25°C, VS = 5V, RL = 25kΩ connected to VS/2, unless otherwise noted.
INPUT BIAS CURRENT
vs TEMPERATURE
0.1Hz TO 10Hz NOISE
10000
100
1µV/div
Input Bias Current (pA)
1000
10
1
0.1
0.01
−50
−25
0
25
50
Temperature (_ C)
75
100
125
2.5s/div
SMALL−SIGNAL OVERSHOOT
vs CAPACITIVE LOAD
NOISE vs FREQUENCY
60
1000
Overshoot (%)
Noise (nV/√Hz)
50
100
40
30
G = +1
20
10
G = −1
0
10
10
100
10k
10
100
SMALL−SIGNAL STEP RESPONSE
LARGE−SIGNAL STEP RESPONSE
500mV/div
Capacitive Load (pF)
25µs/div
6
1k
Frequency (Hz)
20mV/div
1
50µs/div
1000
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SBOS347C − NOVEMBER 2005 − REVISED AUGUST 2006
APPLICATION INFORMATION
+5V
The OPA379 family of operational amplifiers minimizes
power consumption without compromising bandwidth or
noise.
Power-supply
rejection
ratio
(PSRR),
common-mode rejection ratio (CMRR), and open-loop
gain (AOL) typical values are 100dB or better.
When designing for ultra-low power, choose system
components carefully. To minimize current consumption,
select large-value resistors. Any resistors will react with
stray capacitance in the circuit and the input capacitance
of the operational amplifier. These parasitic RC
combinations can affect the stability of the overall system.
A feedback capacitor may be required to assure stability
and limit overshoot or gain peaking.
Good layout practice mandates the use of a 0.1µF bypass
capacitor placed closely across the supply pins.
OPERATING VOLTAGE
OPA379 series op amps are fully specified and tested from
+1.8V to +5.5V. Parameters that vary significantly with
supply voltage are shown in the Typical Characteristics
curves.
INPUT COMMON-MODE VOLTAGE RANGE
The input common-mode voltage range of the OPA379
family typically extends 100mV beyond each supply rail.
This rail-to-rail input is achieved using a complementary
input stage. CMRR is specified from the negative rail to 1V
below the positive rail. Between (V+) − 1V and (V+) + 0.1V,
the amplifier operates with higher offset voltage because
of the transition region of the input stage. See the typical
characteristic, Offset Voltage vs Common-Mode Voltage.
PROTECTING INPUTS FROM
OVER-VOLTAGE
Normally, input currents are 5pA. However, large inputs
(greater than 500mV beyond the supply rails) can cause
excessive current to flow in or out of the input pins.
Therefore, as well as keeping the input voltage below the
maximum rating, it is also important to limit the input
current to less than 10mA. This limiting is easily
accomplished with an input voltage resistor, as shown in
Figure 1.
I OVERLOAD
10mA max
OPA379
VOUT
VIN
5kΩ
Figure 1. Input Current Protection for Voltages
Exceeding the Supply Voltage
NOISE
Although micropower amplifiers frequently have high
wideband noise, the OPA379 series offer excellent noise
performance. Resistors should be chosen carefully
because the OPA379 has only 2.8µVPP of 0.1Hz to 10Hz
noise, and 80nV/√Hz of wideband noise; otherwise, they
can become the dominant source of noise.
CAPACITIVE LOAD AND STABILITY
Follower configurations with load capacitance in excess of
30pF can produce extra overshoot (see typical
characteristic, Small-Signal Overshoot vs Capacitive
Load) and ringing in the output signal. Increasing the gain
enhances the ability of the amplifier to drive greater
capacitive loads. In unity-gain configurations, capacitive
load drive can be improved by inserting a small (10Ω to
20Ω) resistor, RS, in series with the output, as shown in
Figure 2. This resistor significantly reduces ringing while
maintaining DC performance for purely capacitive loads.
However, if there is a resistive load in parallel with the
capacitive load, a voltage divider is created, introducing a
Direct Current (DC) error at the output and slightly
reducing the output swing. The error introduced is
proportional to the ratio RS/RL, and is generally negligible.
V+
RS
VOUT
OPA379
VIN
10Ω to
20Ω
RL
CL
Figure 2. Series Resistor in Unity-Gain Buffer
Configuration Improves Capacitive Load Drive
7
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In unity-gain inverter configuration, phase margin can be
reduced by the reaction between the capacitance at the op
amp input and the gain setting resistors, thus degrading
capacitive load drive. Best performance is achieved by
using smaller valued resistors. However, when large
valued resistors cannot be avoided, a small (4pF to 6pF)
capacitor, CFB, can be inserted in the feedback, as shown
in Figure 3. This configuration significantly reduces
overshoot by compensating the effect of capacitance, CIN,
which includes the amplifier input capacitance and PC
board parasitic capacitance.
1.
Selecting RF: Select RF such that the current through RF
is approximately 1000x larger than the maximum bias
current over temperature:
RF +
+
VREF
1000ǒI BMAXǓ
1.2V
1000(100pA)
+ 12MW [ 10MW
(1)
2.
Choose the hysteresis voltage, VHYST. For batterymonitoring applications, 50mV is adequate.
3.
Calculate R1 as follows:
CFB
Ǔ + 210kW
ǒVV Ǔ + 10MWǒ50mV
2.4V
HYST
R1 + R F
RF
RI
VIN
OPA379
VOUT
CIN
BATT
4.
Select a threshold voltage for VIN rising (VTHRS) = 2.0V
5.
Calculate R2 as follows:
R2 +
CL
+
Figure 3. Improving Capacitive Load Drive
ƪǒ
1
V
THRS
V REF R 1
Ǔ*
1
R1
* R1
ƫ
F
1
1
1
ƪǒ1.2V 2V210kWǓ * 210kW
* 10MW
+ 325kW
BATTERY MONITORING
6.
The low operating voltage and quiescent current of the
OPA379 series make it an excellent choice for battery
monitoring applications, as shown in Figure 4. In this
circuit, VSTATUS will be high as long as the battery voltage
remains above 2V. A low-power reference is used to set
the trip point. Resistor values are selected as follows:
(3)
Calculate RBIAS: The minimum supply voltage for this
circuit will be 1.8V. The REF1112 has a current
requirement of 1.2µA (max). Providing it 2µA of supply
current assures proper operation. Therefore:
R BIAS +
VBATTMIN
+ 1.8V + 0.9MW
I BIAS
2mA
RF
R1
+IN
+
I BIAS
VBATT
RBIAS
−IN
OPA379
OUT
VREF
R2
REF1112
Figure 4. Battery Monitor
8
(2)
VSTATUS
(4)
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LOW-SIDE CURRENT MONITOR
WINDOW COMPARATOR
The micropower OPA379 is well suited for current
monitoring circuits in applications such as a voltage
regulator with fold-back current limiting, or a high-current
power supply with crowbar protection. Figure 5 shows the
OPA379 monitoring the current in a power-supply return
path using a 0.1Ω shunt resistor. The NPN transistor, Q1
(2N2222 or equivalent) is used to generate equal voltages
at the inverting and noninverting inputs. Therefore, the
voltage drops across R1 and RS are equal, and the current
flowing through Q1 is directly proportional to the current
flowing through RS. As the load current increases, the
current through Q1 increases, the voltage drop across R2
increases, and this decreases the output voltage, VOUT, as
shown in Equation (5):
Figure 6 shows the OPA2379 used as a window
comparator. The threshold limits are set by VH and VL, with
VH > VL . When VIN < VH, the output of A1 will be low. When
VIN >VL, the output of A2 will be low. Therefore, both op
amp outputs will be at 0V as long as VIN is between VH and
VL. This results in no current flowing through either diode,
Q1 in cutoff, with the base voltage at 0V, and VOUT forced
high.
V OUT + GND *
ǒRR
2
RS
ǒ
+ 0V * 2.49kW
100W
+ * 2.49W
IL
1
0.1W
Ǔ
IL
If VIN falls below VL, the output of A2 will be high, current
will flow through D2, and VOUT will be low. Likewise, if VIN
rises above VH, the output of A1 will be high, current will
flow through D1, and VOUT will be low.
The window comparator threshold voltages are set as
follows:
VH +
R2
R1 ) R2
(6)
VL +
R4
R3 ) R4
(7)
Ǔ
IL
(5)
3V
3V
R1
5V
VH
R2
2.49kΩ
A1
1/2
OPA2379
R2
D1(2)
3V
R7
5.1kΩ
VOUT
RIN
2kΩ(1)
VOUT
R5
10kΩ
VIN
Q1
Q1(3)
5V
3V
3V
A2
OPA379
R1
100Ω
R6
5.1kΩ
R3
VL
RS
0.1Ω
1/2
OPA2379
D2(2)
R4
Return to Ground
IL
NOTES: (1) RIN protects A1 and A2 from possible excess current flow.
(2) IN4446 or equivalent diodes.
(3) 2N2222 or equivalent NPN transistor.
Figure 5. Low-Side Current Monitor
Figure 6. OPA2379 as a Window Comparator
9
PACKAGE OPTION ADDENDUM
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PACKAGING INFORMATION
Orderable Device
Status (1)
Package
Type
Package
Drawing
Pins Package Eco Plan (2)
Qty
OPA2379AID
ACTIVE
SOIC
D
8
75
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA2379AIDG4
ACTIVE
SOIC
D
8
75
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA2379AIDR
ACTIVE
SOIC
D
8
2500 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA2379AIDRG4
ACTIVE
SOIC
D
8
2500 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AID
ACTIVE
SOIC
D
8
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDBVR
ACTIVE
SOT-23
DBV
5
3000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDBVRG4
ACTIVE
SOT-23
DBV
5
3000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDBVT
ACTIVE
SOT-23
DBV
5
250
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDBVTG4
ACTIVE
SOT-23
DBV
5
250
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDCKR
ACTIVE
SC70
DCK
5
3000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDCKRG4
ACTIVE
SC70
DCK
5
3000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDCKT
ACTIVE
SC70
DCK
5
250
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDCKTG4
ACTIVE
SC70
DCK
5
250
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDG4
ACTIVE
SOIC
D
8
75
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDR
ACTIVE
SOIC
D
8
2500 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA379AIDRG4
ACTIVE
SOIC
D
8
2500 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
75
Lead/Ball Finish
MSL Peak Temp (3)
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
10-Jul-2006
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
Addendum-Page 2
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