RC4157M

www.fairchildsemi.com RC4156/RC4157 High Performance Quad Operational Amplifiers Features • • • • Unity gain bandwidth for RC4156 – 3.5 MHz Unity gain bandwidth for RC4157 – 19 MHz High slew rate for RC4156 – 1.6 V/µS High slew rate for RC4157 – 8.0V/µS • Low noise voltage – 1.4 µVRMS • Indefinite short circuit protection • No crossover distortion Description The RC4156 and RC4157 are monolithic integrated circuits, consisting of four independent high performance operational amplifiers constructed with an advanced epitaxial process. These amplifiers feature improved AC performance which far exceeds that of the 741 type amplifiers. Also featured are excellent input characteristics and low noise, making this device the optimum choice for audio, active filter and instrumentation applications. The RC4157 is a decompensated version of the RC4156 and is AC stable in gain configurations of -5 or greater. Block Diagram Output (A) –Input (A) +Input (A) +Input (B) –Input (B) Output (B) 65-3463-01 Pin Assignments Output (D) –Input (D) +Input (D) +Input (C) Output (A) –Input (A) +Input (A) +VS +Input (B) –Input (B) Output (B) 1 2 3 4 5 6 7 14 13 12 11 10 9 8 65-3463-02 A + D + Output (D) –Input (D) +Input (D) –VS +Input (C) –Input (C) Output (C) + B C + –Input (C) Output (C) REV. 1.0.1 6/13/01 PRODUCT SPECIFICATION RC4156/RC4157 Absolute Maximum Ratings (beyond which the device may be damaged)1 Parameter Supply Voltage Input Voltage2 Differential Input Voltage Output Short Circuit Duration3 PDTA < 50°C Operating Temperature Storage Temperature Junction Temperature Lead Soldering Temperature (60 seconds) For TA > 50°C Derate at SOIC, PDIP DIP SOIC SOIC PDIP 5.0 6.25 SOIC PDIP RC4156/RC4157 0 -65 Indefinite 300 468 70 150 125 300 260 mW mW °C °C °C °C °C mW/°C mW/°C Min Typ Max ±20 ±15 30 Units V V V Notes: 1. Functional operation under any of these conditions is NOT implied. Performance and reliability are guaranteed only if Operating Conditions are not exceeded. 2. For supply voltages less than ±15V, the absolute maximum input voltage is equal to the supply voltage. 3. Short circuit to ground on one amplifier only. Operating Conditions Parameter θJC θJA Thermal resistance Thermal resistance SOIC PDIP Min Typ 60 200 160 Max Units °C/W °C/W °C/W Electrical Characteristics (VS = ±15V, RC = 0°C ≤ TA ≤ +70°C) RC4156/4157 Parameters Input Offset Voltage Input Offset Current Input Bias Current Large Signal Voltage Gain Output Voltage Swing Supply Current Average Input Offset Voltage Drift RL ≥ 2 kΩ,VOUT ±10V RL ≥ 2 kΩ 15 ±10 10 5.0 Test Conditions RS ≤ 10 kΩ Min Typ Max 6.5 100 400 Units mV nA nA V/mV V mA µV/°C 2 REV. 1.0.1 6/13/01 RC4156/RC4157 PRODUCT SPECIFICATION Electrical Characteristics (VS = ±15V and TA = +25°C unless otherwise noted) RC4156/4157 Parameters Input Offset Voltage Input Offset Current Input Bias Current Input Resistance Large Signal Voltage Gain Output Voltage Swing Input Voltage Range Output Resistance Short Circuit Current Common Mode Rejection Ratio Power Supply Rejection Ratio Supply Current (All Amplifiers) Transient Response (4156) Rise Time Overshoot Slew Rate Unity Gain Bandwidth (4156) Phase Margin (4156) Transient Response (4157) Rise Time Overshoot Slew Rate Unity Gain Bandwidth (4157) Phase Margin (4157) Power Bandwidth Input Noise Voltage 1 Input Noise Current Channel Separation Note: 1. Sample tested only. Test Conditions RS ≤ 10 kΩ Min Typ 1.0 30 60 0.5 Max 5.0 50 300 Units mV nA nA MΩ V/mV V V V Ω mA dB dB RL ≥ 2 kΩ, VOUT ±10V RL ≥ 10 kΩ RL ≥ 2 kΩ 25 ±12 ±10 ±12 100 ±14 ±13 ±14 230 25 RS ≤ 10 kΩ RS ≤ 10 kΩ RL = ∞ 80 80 5.0 60 25 1.3 2.8 1.6 3.5 50 50 25 6.5 8.0 19 50 20 25 1.4 15 108 5.0 7.0 mA nS % V/µS MHz % nS % V/µS MHz % kHz µVRMS pARMS dB RL = 2 kΩ, CL = 50 pF AV = -5 AV = -5 AV = -5, RL = 2 kΩ, CL = 50 pF VOUT = 20Vp-p F = 20 Hz to 20 kHz F = 20 Hz to 20 kHz 15 REV. 1.0.1 6/13/01 3 PRODUCT SPECIFICATION RC4156/RC4157 Typical Performance Characteristics 140 110 100 90 80 70 60 50 40 30 20 10 0 -10 4156 AVOL Φ 120 PSRR (dB) R L = 2K C L = 55 pF +VS -VS 0 45 90 135 180 65-0738 100 80 60 40 20 0 -100 -75 -50 -25 AVOL (dB) Φ (Deg) 1 10 100 1K 10K 100K 1M F (Hz) 10M 0 +25 +50 +75 +100 +125 +150 TA (°C) Figure 1. Open Loop Gain, Phase vs. Frequency Figure 2. PSRR vs. Temperature -140 -120 -100 CS (dB) -80 -60 -40 -20 0 10 100 1K F (Hz) Figure 3. Channel Separation vs. Frequency 10K 100K 1K 1K 6 5 1K 1K 2 3 100K 4156/57 1 VOUT1 VOUT2 C.S. = 20 log ( ) 100 VOUT1 100K 4156/57 7 VOUT2 65-0739 1.3 35 Transient Response (Normalized to +25°C) 1.2 1.1 en (nV Hz ) 1.0 0.9 0.8 0.7 65-0741 1.4 1.2 IN (pA Hz ) 65-0742 30 25 20 15 10 5 0 10 100 en IN 1.0 0.8 0.6 0.4 0.2 10K 0 100K 0.6 -100 -75 -50 -25 0 +25 +50 +75 +100+125+150 TA (°C) Figure 4. Transient Response vs. Temperature 1K F (Hz) Figure 5. Input Noise Voltage, Current Density vs. Frequency 4 REV. 1.0.1 6/13/01 65-0740 RC4156/RC4157 PRODUCT SPECIFICATION Typical Performance Characteristics (continued) 1.3 SR,BW (Normalized to +25°C) SR, BW (Normalized to ±15V) 1.2 1.1 1.0 0.9 0.8 0.7 0.6 -100 -50 0 +50 TA (°C) Figure 6. Slew Rate, Bandwidth vs. Temperature +100 65-0743 1.1 BW 1.0 SR and BW 0.9 0.8 65-0744 0.7 +150 0 ±2 ±5 ±10 ±VS (V) ±15 ±20 Figure 7. Slew Rate, Bandwidth vs. Supply Voltage 30 30 VOUT P-P (V) 10 VOUT P-P = 28V VS = ±15V VOUT P-P = 18V VS = ±10V VOUT P-P = 8V VS = ±5V 25 VOUT P-P (V) 65-0746 20 15 10 65-0749 1.0 4156 (Voltage Follower) R L = Open C L = 50 pF 05 0 100 1K RL (Ω ) Figure 9. Output Voltage Swing vs. Load Resistance 10K 0.1 100 1K 10K F (Hz) 100K 1M 100K Figure 8. Output Voltage Swing vs. Frequency 70 60 50 ΦM (Deg) 40 30 20 10 0 10 100 1K CL (pF) 10K BW ΦM 4156 7 6 5 4 3 2 1 0 100K 65-0745 Figure 10. Small Signal Phase Margin, Unity Gain Bandwidth vs. Load Capacitance BW (MHz) REV. 1.0.1 6/13/01 5 PRODUCT SPECIFICATION RC4156/RC4157 Typical Performance Characteristics (continued) 140 120 100 CMRR (dB) 65-0747 140 120 100 IB IB, IOS (nA) 80 60 40 20 0-100 -75 -50 -25 80 60 40 20 0 -100 -75 -50 -25 65-0748 IOS 0 +25 +50 +75+100+125+150 TA (°C) 0 +25 +50 +75+100+125+150 TA (°C) Figure 11. Input Bias, Offset Current vs. Temperature Figure 12. CMRR vs. Temperature Applications The RC4156 and RC4157 quad operational amplifiers can be used in almost any 741 application and will provide superior performance. The higher unity gain bandwidth and slew rate make it ideal for applications requiring good frequency response, such as active filter circuits, oscillators and audio amplifiers. The following applications have been selected to illustrate the advantages of using the Fairchild Semiconductor RC4156 and RC4157 quad operational amplifiers. positive then negative, and the comparator switching in a square wave fashion. The amplitude of V2 is adjusted by varying R1. For best operation, it is recommended that R1 and VR be set to obtain a triangle wave at V2 with ±12V amplitude. This will then allow A3 and A4 to be used for independent adjustment of output-offset and amplitude over a wide range. The triangle wave frequency is set by C0, R0, and the maximum output voltages of the comparator. A more symmetrical waveform can be generated by adding a back-to-back Zener diode pair as shown in Figure 14. An asymmetric triangle wave is needed in some applications. Adding diodes as shown by the dashed lines is a way to vary the positive and negative slopes independently. The frequency range can be very wide and the circuit will function well up to about 10 kHz. The square wave transition time at V1 is less than 21 µS when using the RC4156. Triangle and Square Wave Generator The circuit of Figure 13 uses a positive feedback loop closed around a combined comparator and integrator. When power is applied the output of the comparator will switch to one of two states, to the maximum positive or maximum negative voltage. This applies a peak input signal to the integrator, and the integrator output will ramp either down or up, opposite of the input signal. When the integrator output (which is connected to the comparator input) reaches a threshold set by R1 and R2, the comparator will switch to the opposite polarity. This cycle will repeat endlessly, the integrator charging 6 REV. 1.0.1 6/13/01 RC4156/RC4157 PRODUCT SPECIFICATION +12V (+) +15V VR ~ 0.12V ~ 30K Square Wave Output R0 1K 2 3 4156/57 A R1 20K R2 20K 5K -15V 1K Integrator 5K +15V 12 * Optional – asymmetric ramp slopes -15V 5K Output Offset 13 4156/57 D 14 V3 65-0750 -12V R4 C0 1K 6 100K * 10K 4156/57 5 B 7 V2 R3 20K 9 4 8 V4 Triangle Wave Output 20K +15V Amplitude Adjust 1 V1 4156/57 10 C 11 Comparator Figure 13. Triangle and Square Wave Generator 10K R1 65-2051 Figure 14. Triangle Generator—Symmetrical Output Option Active Filters The introduction of low-cost quad op amps has had a strong impact on active filter design. The complex multiplefeedback, single op amp filter circuits have been rendered obsolete for most applications. State-variable active-filter circuits using three to four op amps per section offer many advantages over the single op amp circuits. They are relatively insensitive to the passive-component tolerances and variations. The Q, gain, and natural frequency can be independently adjusted. Hybrid construction is very practical because resistor and capacitor values are relatively low and the filter parameters are determined by resistance ratios rather than by single resistors. A generalized circuit diagram of the 2-pole state-variable active filter is shown in Figure 15. The particular input connections and component-values can be calculated for specific applications. An important feature of the state-variable filter is that it can be inverting or non-inverting and can simultaneously provide three outputs: lowpass, bandpass, and highpass. A notch filter can be realized by adding one summing op amp. The RC4156 was designed and characterized for use in active filter circuits. Frequency response is fully specified with minimum values for unity-gain bandwidth, slew-rate, and full-power response. Maximum noise is specified. Output swing is excellent with no distortion or clipping. The RC4156 provides full, undistorted response up to 20 kHz and is ideal for use in high-performance audio and telecommunication equipment. In the state-variable filter circuit, one amplifier performs a summing function and the other two act as integrators. The choice of passive component values is arbitrary, but must be consistent with the amplifier operating range and input signal 7 REV. 1.0.1 6/13/01 PRODUCT SPECIFICATION RC4156/RC4157 R5 100K R4 10K V1 R3* 2 4156/57 3 A 1 R1** 6 4156/57 5 B 7 10 R2** 9 4156/57 C 8 C1 1000 pF C2 1000 pF VN R8* R7* R6 100K VHP Highpass Ouput V BP Bandpass Output VLP Lowpass Output * Input connections are chosen for inverting or non-inverting response. Values of R3,R7,R8 determine gain and Q. ** Values of R1 and R2 determine natural frequency. 65-0751 Figure 15. 2-Pole State-Variable Active Filter characteristics. The values shown for C1, C2, R4, R5 and R6 are arbitrary. Pre-selecting their values will simplify the filter tuning procedures, but other values can be used if necessary. The generalized transfer function for the state-variable active filter is: a2 s + a1 s + a0 T ( s ) = ----------------------------------2 s + b1 s + b0 2 The input configuration determines the polarity (inverting or non-inverting), and the output selection determines the type of filter response (lowpass, bandpass, or highpass). Notch and all-pass configurations can be implemented by adding another summing amplifier. Bandpass filters are of particular importance in audio and telecommunication equipment. A design approach to bandpass filters will be shown as an example of the state-variable configuration. Filter response is conventionally described in terms of a natural frequency ω0 in radians/sec, and Q, the quality of the complex pole pair. The filter parameters ω0 and Q relate to the coefficients in T(s) as: ω0 = ω0 b 0 and Q = ----b0 Design Example Bandpass Filter For the bandpass active filter (Figure 16) the input signal is applied through R3 to the inverting input of the summing amplifier and the output is taken from the first integrator (VBP). The summing amplifier will maintain equal voltage at the inverting and non-inverting inputs (see Equation 1). R3R5 R3R4 R4R5 ---------------------------------------------------------R3 + R5 R3 + R4 R4 + R5 R7 ---------------------------------- V HP ( s ) + ---------------------------------- V LP ( s ) + ---------------------------------- V IN ( s ) + -------------------- V BP ( s ) R3R5 R3R4 R4R5 R6 + R7 R4 + -------------------R5 + -------------------R3 + -------------------R3 + R5 R3 + R4 R4 + R5 Equation 1. 8 REV. 1.0.1 6/13/01 RC4156/RC4157 PRODUCT SPECIFICATION R5 100K R4 10K 2 1 3 R7 RC4156/57 A R6 100K R1 Set Center Frequency VIN Trim Gain and Q R3 6 5 C1 1000 pF 7 R2 9 10 C2 1000 pF 8 RC4156/57 C RC4156/57 B VBP 65-0752 Figure 16. Bandpass Active Filter These equations can be combined to obtain the transfer function: 1 -V V BP ( s ) = – ----------------- HP ( s ) R1C1S and 1 -V V LP ( s ) = – ----------------- BP ( s ) R2C2S R4 1 ------ ⋅ -------------- S V BP ( s ) R3 R1C1 ----------------- = -----------------------------------------------------------------------------------------------------------------------------------------------------V IN ( s ) 1 R7 R4 1 2 R4 R4 S + --------------------  1 + ------ + ------   -------------- S +  ------   -----------------------------   R5  R1C1R2C2 R6 + R7  R5 R3  R1C1 Defining 1/R1C1 as ω1, 1/R2C2 as ω2, and substituting in the assigned values for R4, R5, and R6, then the transfer function simplifies to: 10 ------- ⋅ ω 1 s V BP ( s ) R3 ----------------- = ---------------------------------------------------------------------V IN ( s ) 4 10 1.1 + ------R3 2 1 S + --------------------- ω 1 s + -----------5 ω1 ω2 10 1 + ------R7 (dB) 4 0 -10 -20 -30 -40 -50 -60 0.1 1.0 Q = 0.5 Q = 1.0 Q = 2.0 Q = 5.0 Q = 10 Q = 20 Q = 50 Q = 100 65-0753 10 This is now in a convenient form to look at the centerfrequency ω0 and filter Q. ω0 = 0.1 ω 1 ω 2 –9 ω ωo VBP = V IN ω ωo 1- 1 Q + 1 Q ω 0 = 10 0.1R1R2 and 5 ω ωo 22 ω ωo 2 10 1 + ------R7 Q = --------------------- ω 0 4 10 1.1 + ------R3 Figure 17. Bandpass Transfer Characteristics Normalized for Unity Gain and Frequency The frequency responses for various values of Q are shown in Figure 17. REV. 1.0.1 6/13/01 9 PRODUCT SPECIFICATION RC4156/RC4157 These equations suggest a tuning sequence where ω is first trimmed via R1 or R2, then Q is trimmed by varying R7 and/or R3. An important advantage of the state-variable bandpass filter is that Q can be varied without affecting center frequency ω0. This analysis has assumed ideal op amps operating within their linear range, which is a valid design approach for a reasonable range of ω0 and Q. At extremes of ω0 and at high values of Q, the op amp parameters become significant. A rigorous analysis is very complex, but some factors are particularly important in designing active filters. 1. The passive component values should be chosen such that all op amps are operating within their linear region for the anticipated range of input signals. Slew rate, output current rating, and common-mode input range must be considered. For the integrators, the current through the feedback capacitor (I = C dV/dt) should be included in the output current computations. 2. From the equation for Q, it should seem that infinite Q could be obtained by making R7 zero. But as R7 is made small, the Q becomes limited by the op amp gain at the frequency of interest. The effective closed-loop gain is being increased directly as R7 is made smaller, and the ratio of open-loop gain to closed-loop gain is becoming less. The gain and phase error of the filter at high Q is very dependent on the op amp open-loop gain at w0. The attenuation at extremes of frequency is limited by the op amp gain and unity-gain bandwidth. For integrators, the finite open-loop op amp gain limits the accuracy at the low-end. The open-loop roll-off of gain limits the filter attenuation at high frequency. 3. The RC4156 quad operational amplifier has much better frequency response than a conventional 741 circuit and is ideal for active filter use. Natural frequencies of up to 10 kHz are readily achieved and up to 20 kHz is practical for some configurations. Q can range up to 50 with very good accuracy and up to 500 with reasonable response. The extra gain of the RC4156 at high frequencies gives the quad op amp an extra margin of performance in active-filter circuits. Schematic Diagram (1/4 shown) (4) +Vs R1 4900 Q3 Q2 (2,6,9,13) - Input + Input Q4 (3,5,10,12) D2 C1 R7 20 Q7 Q17 Q10 Q9 R3 18K 65-0735 Q1 R9 30 Q13 Q5 R5 30K Q12 Q16 R6 20 R8 150 To Next Amplifier Q15 (1,7,8,14) Outputs F1 Q6 Q8 Q11 R4 22K Q14 R2 10K D1 (11) -Vs 10 REV. 1.0.1 6/13/01 RC4156/RC4157 PRODUCT SPECIFICATION Mechanical Dimensions (continued) 14-Lead Plastic DIP Package Inches Min. A A1 A2 B B1 C D D1 E E1 e eB L N — .015 .115 Max. Millimeters Min. — .38 2.93 Max. Notes: Notes 1. Dimensioning and tolerancing per ANSI Y14.5M-1982. 2. "D" and "E1" do not include mold flashing. Mold flash or protrusions shall not exceed .010 inch (0.25mm). 3. Terminal numbers are shown for reference only. 4. "C" dimension does not include solder finish thickness. 5. Symbol "N" is the maximum number of terminals. 4 2 Symbol .210 — .195 .014 .022 .045 .070 .008 .015 .725 .795 .005 — .300 .325 .240 .280 .100 BSC — .430 .115 .200 14 5.33 — 4.95 .36 .56 1.14 1.78 .20 .38 18.42 20.19 .13 — 7.62 8.26 6.10 7.11 2.54 BSC — 10.92 2.92 5.08 14 2 5 D 7 1 E1 D1 8 14 E e A A1 L B1 B eB C REV. 1.0.1 6/13/01 11 PRODUCT SPECIFICATION RC4156/RC4157 Mechanical Dimensions (continued) 14-Lead SOIC Package Inches Min. A A1 B C D E e H h L N α ccc .053 .004 .013 .008 .336 Max. .069 .010 .020 .010 .345 Millimeters Min. 1.35 0.10 0.33 0.19 8.54 Max. 1.75 0.25 0.51 0.25 8.76 5 2 2 Notes: Notes 1. Dimensioning and tolerancing per ANSI Y14.5M-1982. 2. "D" and "E" do not include mold flash. Mold flash or protrusions shall not exceed .010 inch (0.25mm). 3. "L" is the length of terminal for soldering to a substrate. 4. Terminal numbers are shown for reference only. 5. "C" dimension does not include solder finish thickness. 6. Symbol "N" is the maximum number of terminals. Symbol .150 .158 .050 BSC .228 .244 .010 .016 14 0° — 8° .004 .020 .050 3.81 4.01 1.27 BSC 5.79 6.20 0.25 0.40 14 0° — 8° 0.10 0.50 1.27 3 6 14 8 E H 1 7 D A1 A SEATING PLANE –C– LEAD COPLANARITY ccc C α h x 45° C e B L 12 REV. 1.0.1 6/13/01 PRODUCT SPECIFICATION RC4156/RC4157 Ordering Information Product Number RC4156N RC4157N RC4156M RC4157M Temperature Range 0° to 70°C 0° to 70°C 0° to 70°C 0° to 70°C Screening Commercial Commercial Commercial Commercial Package 14 Pin Plastic DIP 14 Pin Plastic DIP 14 Pin Wide SOIC 14 Pin Wide SOIC Package Marking RC4156N RC4157N RC4156M RC4157M DISCLAIMER FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO ANY PRODUCTS HEREIN TO IMPROVE RELIABILITY, FUNCTION OR DESIGN. FAIRCHILD DOES NOT ASSUME ANY LIABILITY ARISING OUT OF THE APPLICATION OR USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HEREIN; NEITHER DOES IT CONVEY ANY LICENSE UNDER ITS PATENT RIGHTS, NOR THE RIGHTS OF OTHERS. LIFE SUPPORT POLICY FAIRCHILD’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF FAIRCHILD SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. www.fairchildsemi.com 6/13/01 0.0m 003 Stock#DS30004841 © 2001 Fairchild Semiconductor Corporation 2. A critical component in any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness.