LMP7731MFX

LMP7731, Low Noise, Precision, RRIO, Amplifier in SOT23–5 July 2007 LMP7731 2.9 nV/sqrt(Hz) Low Noise, Precision, RRIO, Operational Amplifier in SOT23-5 General Description The LMP7731 is a single, low noise, low offset voltage, railto-rail input and output, low voltage precision amplifier. The LMP7731 is part of the LMP® precision amplifier family and is ideal for precision and low noise applications with low voltage requirements. This operational amplifier offers low voltage noise of 2.9 nV/ with a 1/f corner of only 3 Hz and low DC offset with a maximum value of ±40 µV, targeting high accuracy, low frequency applications. The LMP7731 has bipolar input stages with a bias current of only 1.5 nA. This low input bias current, complemented by the very low AC and DC levels of voltage noise, makes the LMP7731 an excellent choice for photometry applications. The LMP7731 provides a wide GBW of 22 MHz while consuming only 2 mA of current. This high gain bandwidth along with the high open loop gain of 130 dB enables accurate signal conditioning in applications with high closed loop gain requirements. The LMP7731 has a supply voltage range of 1.8V to 5.5V, making it an ideal choice for battery operated portable applications. The LMP7731 is offered in a 5-pin SOT23 package. Features (Typical values, TA = 25°C, VS = 5V) ■ Input voltage noise — f = 3 Hz — f = 1 kHz ■ Offset voltage (max) ■ Offset voltage drift (max) ■ CMRR ■ Open loop gain ■ GBW ■ Slew rate ■ THD @ f = 10 kHz, AV = +1, RL = 2 kΩ ■ Supply current per channel ■ Supply voltage range ■ Operating temperature range ■ Input bias current ■ RRIO ■ 5-Pin SOT23 package 3.3 nV/√Hz 2.9 nV/√Hz ±40 µV ±1.0 µV/°C 130 dB 130 dB 22 MHz 2.4 V/µs 0.001% 2.2 mA 1.8V to 5.5V −40°C to 125°C ±1.5 nA Applications ■ ■ ■ ■ Thermopile amplifier Gas analysis instruments Photometric instrumentation Medical instrumentation Typical Application Thermopile Signal Amplifier 20175201 LMP® is a registered trademark of National Semiconductor Corporation. © 2007 National Semiconductor Corporation 201752 www.national.com LMP7731 Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. ESD Tolerance (Note 2) Human Body Model Inputs pins only All other pins Machine Model Charge Device Model VIN Differential Supply Voltage (VS = V+ – V−) Storage Temperature Range Junction Temperature (Note 3) Soldering Information Infrared or Convection (20 sec) Wave Soldering Lead Temp. (10 sec) −65°C to 150°C +150°C max 235°C 260°C 2000V 2000V 200V 1000V ±2V 6.0V (Note 4) Operating Ratings Temperature Range Supply Voltage (VS = V+ – V–) (Note 1) −40°C to 125°C 1.8V to 5.5V 265°C/W Package Thermal Resistance (θJA) 5-Pin SOT23 2.5V Electrical Characteristics Symbol VOS Parameter Input Offset Voltage (Note 7) Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 2.5V, V− = 0V, VCM = V+/2, RL >10 kΩ to V+/2. Boldface limits apply at the temperature extremes. Conditions VCM = 2.0V VCM = 0.5V TCVOS Input Offset Voltage Drift Input Offset Voltage Time Drift IB Input Bias Current VCM = 2.0V VCM = 0.5V VCM = 0.5V and VCM = 2.0V VCM = 2.0V VCM = 0.5V IOS Input Offset Current VCM = 2.0V VCM = 0.5V TCIOS CMRR Input Offset Current Drift Common Mode Rejection Ratio VCM = 0.5V and VCM = 2.0V 0.15V ≤ VCM ≤ 0.7V 1.5V ≤ VCM ≤ 2.35V PSRR Power Supply Rejection Ratio 2.5V ≤ V+ ≤ 5V 1.8V ≤ V+ ≤ 5.5V CMVR AVOL Input Common-Mode Voltage Range Large Signal Voltage Gain Large Signal CMRR ≥ 80 dB RL = 10 kΩ to V+/2 VO = 0.5V to 2.0V RL = 2 kΩ to V+/2 VO = 0.5V to 2.0V 0 112 104 109 90 130 119 dB 0.23V ≤ VCM ≤ 0.7V 1.5V ≤ VCM ≤ 2.27V 101 89 105 99 111 105 Min (Note 6) Typ (Note 5) ±9 ±9 ±0.5 ±0.2 0.35 ±1 ±12 ±1 ±11 0.0474 120 dB ±30 ±45 ±50 ±75 ±50 ±75 ±60 ±80 Max (Note 6) ±50 ±120 ±40 ±100 ±1.0 ±0.8 Units μV μV/°C μV/month nA nA nA/°C 129 129 dB 117 2.5 V www.national.com 2 LMP7731 Symbol VO Parameter Output Swing High Conditions RL = 10 kΩ to V+/2 RL = 2 kΩ to V+/2 Min (Note 6) Typ (Note 5) 4 13 6 9 Max (Note 6) 50 75 50 75 50 75 50 75 Units Output Swing Low RL = 10 kΩ to V+/2 RL = 2 kΩ to V+/2 mV from either rail IO Output Short Circuit Current Sourcing, VO = V+/2 VIN (diff) = 100 mV Sinking, VO = V+/2 VIN (diff) = −100 mV 22 12 15 10 31 44 2.0 2.3 2.7 3.4 3.1 3.9 mA IS Supply Current (Per Channel) VCM = 2.0V VCM = 0.5V mA SR GBW GM ΦM RIN THD+N en Slew Rate Gain Bandwidth Product Gain Margin Phase Margin Input Resistance Total Harmonic Distortion Input-Referred Voltage Noise 0.1 Hz to 10 Hz AV = +1, CL = 10 pF, RL = 10 kΩ to V+/2, VO = 2 VPP CL = 20 pF, RL = 10 kΩ to V+/2 CL = 20 pF, RL = 10 kΩ to V+/2 CL = 20 pF, RL = 10 kΩ to V+/2 Differential Mode Common Mode AV = 1, f = 1 kHz, Amplitude = 1V f = 1 kHz, VCM = 2.0V f = 1 kHz, VCM = 0.5V 2.4 21 14 60 38 151 0.002 3 3 75 1.1 2.3 V/μs MHz dB deg kΩ MΩ % nV/ nVPP pA/ in Input-Referred Current Noise f = 1 kHz, VCM = 2.0V f = 1 kHz, VCM = 0.5V 3.3V Electrical Characteristics Symbol VOS Parameter Input Offset Voltage (Note 7) (Note 4) Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 3.3V, V− = 0V, VCM = V+/2, RL > 10 kΩ to V+/2. Boldface limits apply at the temperature extremes. Conditions VCM = 2.5V VCM = 0.5V TCVOS Input Offset Voltage Drift Input Offset Voltage Time Drift IB Input Bias Current VCM = 2.5V VCM = 0.5V VCM = 0.5V and VCM = 2.5V VCM = 2.5V VCM = 0.5V IOS Input Offset Current VCM = 2.5V VCM = 0.5V Min (Note 6) Typ (Note 5) ±6 ±6 ±0.5 ±0.2 0.35 ±1.5 ±13 ±1 ±11 ±30 ±45 ±50 ±77 ±50 ±70 ±60 ±80 Max (Note 6) ±50 ±120 ±40 ±100 ±1.0 ±0.8 Units μV μV/°C μV/month nA nA 3 www.national.com LMP7731 Symbol TCIOS CMRR Parameter Input Offset Current Drift Common Mode Rejection Ratio Conditions VCM = 0.5V and VCM = 2.5V 0.15V ≤ VCM ≤ 0.7V 1.5V ≤ VCM ≤ 3.15V 0.23V ≤ VCM ≤ 0.7V 1.5V ≤ VCM ≤ 3.07V Min (Note 6) Typ (Note 5) 0.048 120 Max (Note 6) Units nA/°C 101 89 105 99 111 105 0 112 104 110 92 130 dB PSRR Power Supply Rejection Ratio 2.5V ≤ V+ ≤ 5.0V 1.8V ≤ V+ ≤ 5.5V 129 dB 117 3.3 130 119 5 14 9 13 50 75 50 75 50 75 50 75 mV from either rail dB V CMVR AVOL Input Common-Mode Voltage Range Large Signal Voltage Gain Large Signal CMRR ≥ 80 dB RL = 10 kΩ to V+/2 VO = 0.5V to 2.8V RL = 2 kΩ to V+/2 VO = 0.5V to 2.8V VO Output Swing High RL = 10 kΩ to V+/2 RL = 2 kΩ to V+/2 Output Swing Low RL = 10 kΩ to V+/2 RL = 2 kΩ to V+/2 IO Output Short Circuit Current Sourcing, VO = V+/2 VIN (diff) = 100 mV Sinking, VO = V+/2 VIN (diff) = -100 mV 28 22 25 20 45 48 2.1 2.4 2.4 22 14 62 38 151 0.002 2.9 2.9 65 1.1 2.1 pA/ nV/ nVPP 2.8 3.5 3.2 4.0 mA IS Supply Current (Per Channel) VCM = 2.5V VCM = 0.5V mA SR GBW GM ΦM RIN THD+N en Slew Rate Gain Bandwidth Product Gain Margin Phase Margin Input Resistance Total Harmonic Distortion Input-Referred Voltage Noise 0.1 Hz to 10 Hz AV = +1, CL = 10 pF, RL = 10 kΩ to V+/2, VO = 2 VPP CL = 20 pF, RL = 10 kΩ to V+/2 CL = 20 pF, RL = 10 kΩ to Differential Mode Common Mode AV = 1, f = 1 kHz, Amplitude = 1V, f = 1 kHz, VCM = 2.5V f = 1 kHz, VCM = 0.5V V+/2 CL = 20 pF, RL = 10 kΩ to V+/2 V/μs MHz dB deg kΩ MΩ % in Input-Referred Current Noise f = 1 kHz, VCM = 2.5V f = 1 kHz, VCM = 0.5V www.national.com 4 LMP7731 5V Electrical Characteristics Symbol VOS Parameter Input Offset Voltage (Note 7) (Note 4) Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 5V, V− = 0V, VCM = V+/2, RL > 10 kΩ to V+/2. Boldface limits apply at the temperature extremes. Conditions VCM = 4.5V VCM = 0.5V TCVOS Input Offset Voltage Drift Input Offset Voltage Time Drift IB Input Bias Current VCM = 4.5V VCM = 0.5V VCM = 0.5V and VCM = 4.5V VCM = 4.5V VCM = 0.5V IOS Input Offset Current VCM = 4.5V VCM = 0.5V TCIOS CMRR Input Offset Current Drift Common Mode Rejection Ratio VCM = 0.5V and VCM = 4.5V 0.15V ≤ VCM ≤ 0.7V 1.5V ≤ VCM ≤ 4.85V PSRR Power Supply Rejection Ratio 2.5V ≤ V+ ≤ 5V 1.8V ≤ V+ ≤ 5.5V CMVR AVOL Input Common-Mode Voltage Range Large Signal Voltage Gain Large Signal CMRR ≥ 80 dB RL = 10 kΩ to V+/2 VO = 0.5V to 4.5V RL = 2 kΩ to V+/2 VO = 0.5V to 4.5V VO Output Swing High RL = 10 kΩ to V+/2 RL = 2 kΩ to V+/2 Output Swing Low RL = 10 kΩ to V+/2 RL = 2 kΩ to V+/2 IO Output Short Circuit Current Sourcing, VO = V+/2 VIN (diff) = 100 mV Sinking, VO = V+/2 VIN (diff) = -100 mV IS Supply Current (Per Channel) VCM = 4.5V VCM = 0.5V SR Slew Rate AV = +1, CL = 10 pF, RL = 10 kΩ to V+/2, VO = 2 VPP 33 27 30 25 0 112 104 110 94 130 119 8 24 9 23 47 49 2.2 2.5 3.0 3.7 3.4 4.2 mA 50 75 50 75 50 75 50 75 mV from either rail dB 0.23V ≤ VCM ≤ 0.7V 1.5V ≤ VCM ≤ 4.77V 101 89 105 99 111 105 Min (Note 6) Typ (Note 5) ±6 ±6 ±0.5 ±0.2 0.35 ±1.5 ±14 ±1 ±11 0.0482 120 dB ±30 ±50 ±50 ±85 ±50 ±70 ±65 ±80 Max (Note 6) ±50 ±120 ±40 ±100 ±1.0 ±0.8 μV/month Units μV μV/°C nA nA nA/°C 130 129 dB 117 5 V mA 2.4 V/μs 5 www.national.com LMP7731 Symbol GBW GM ΦM RIN THD+N en Parameter Gain Bandwidth Product Gain Margin Phase Margin Input Resistance Total Harmonic Distortion Input-Referred Voltage Noise 0.1 Hz to 10 Hz Conditions CL = 20 pF, RL = 10 kΩ to V+/2 CL = 20 pF, RL = 10 kΩ to Differential Mode Common Mode AV = 1, f = 1 kHz, Amplitude = 1V f = 1 kHz, VCM = 4.5V f = 1 kHz, VCM = 0.5V V+/2 CL = 20 pF, RL = 10 kΩ to V+/2 Min (Note 6) Typ (Note 5) 22 12 65 38 151 0.001 2.9 2.9 78 1.1 2.2 Max (Note 6) Units MHz dB deg kΩ MΩ % nV/ nVPP pA/ in Input-Referred Current Noise f = 1 kHz, VCM = 4.5V f = 1 kHz, VCM = 0.5V Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics Tables. Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC) Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC). Note 3: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) – TA)/ θJA. All numbers apply for packages soldered directly onto a PC Board. Note 4: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of the device such that TJ = TA. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self-heating where TJ > TA. Absolute maximum Ratings indicate junction temperature limits beyond which the device maybe permanently degraded, either mechanically or electrically. Note 5: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material. Note 6: All limits are guaranteed by testing, statistical analysis or design. Note 7: Ambient production test is performed at 25°C with a variance of ±3°C. Connection Diagram 5-Pin SOT23 20175202 Top View Ordering Information Package 5-Pin SOT23 Part Number LMP7731MF LMP7731MFX Package Marking AY3A Transport Media 1k Units Tape and Reel 3k Units Tape and Reel NSC Drawing MF05A www.national.com 6 LMP7731 Typical Performance Characteristics Offset Voltage Distribution Unless otherwise noted: TA = 25°C, RL > 10 kΩ, VCM = VS/2. TCVOS Distribution 20175238 20175234 Offset Voltage Distribution TCVOS Distribution 20175239 20175236 Offset Voltage Distribution TCVOS Distribution 20175240 20175235 7 www.national.com LMP7731 Offset Voltage Distribution TCVOS Distribution 20175241 20175237 Offset Voltage vs. Temperature Offset Voltage vs. Temperature 20175251 20175252 PSRR vs. Frequency CMRR vs. Frequency 20175229 20175256 www.national.com 8 LMP7731 Offset Voltage vs. Supply Voltage Offset Voltage vs. VCM 20175242 20175243 Offset Voltage vs. VCM Offset Voltage vs. VCM 20175244 20175245 Input Offset Voltage Time Drift Slew Rate vs. Supply Voltage 20175230 20175220 9 www.national.com LMP7731 Input Voltage Noise vs. Frequency Input Current Noise vs. Frequency 20175261 20175262 Time Domain Voltage Noise Time Domain Voltage Noise 20175269 20175267 Time Domain Voltage Noise Output Voltage vs. Output Current 20175268 20175259 www.national.com 10 LMP7731 Input Bias Current vs. VCM Input Bias Current vs. VCM 20175225 20175226 Input Bias Current vs. VCM Open Loop Frequency Response Over Temperature 20175227 20175218 Open Loop Frequency Response Open Loop Frequency Response 20175219 20175228 11 www.national.com LMP7731 THD+N vs. Frequency THD+N vs. Output Voltage 20175257 20175258 Large Signal Step Response Small Signal Step Response 20175222 20175221 Large Signal Step Response Small Signal Step Response 20175224 20175223 www.national.com 12 LMP7731 Supply Current vs. Supply Voltage Output Swing High vs. Supply Voltage 20175246 20175250 Output Swing Low vs. Supply Voltage Sinking Current vs, Supply Voltage 20175249 20175247 Sourcing Current vs. Supply Voltage 20175248 13 www.national.com LMP7731 Application Information LMP7731 The LMP7731 is a single, low noise, low offset voltage, railto-rail input and output, and low voltage precision amplifier. with a 1/f corThe low input voltage noise of only 2.9 nV/ ner at 3 Hz makes the LMP7731 ideal for sensor applications where DC accuracy is of importance. The LMP7731 has a very low guaranteed offset voltage of only ±40 µV. This low offset voltage along with the very low input voltage noise allows higher signal integrity and higher signal to noise ratios as the error contribution by the amplifier is at a minimum. The LMP7731 has a high gain bandwidth of 22 MHz. This wide bandwidth enables use of the amplifier at higher gain settings while retaining usable bandwidth for the application. This is particularly beneficial when system designers need to use sensors with very limited output voltage range as it allows larger gains in one stage which in turn increases the signal to noise ratio. The LMP7731 has proprietary input bias cancellation circuitry on the input stages. This allows the LMP7731 to have only about 1.5 nA bias current with a bipolar input stage. This low input bias current, paired with the inherent lower input voltage noise of bipolar input stages makes the LMP7731 an excellent choice for precision applications. The combination of low input bias current, low input offset voltage, and low input voltage noise enables the user to achieve unprecedented accuracy and higher signal integrity. National Semiconductor is heavily committed to precision amplifiers and the market segment they serve. Technical support and extensive characterization data are available for sensitive applications or applications with a constrained error budget. The LMP7731 is offered in the space saving 5-Pin SOT23 package. This small package is an ideal solution for area constrained PC boards and portable electronics. INPUT BIAS CURRENT CANCELLATION The LMP7731 has proprietary input bias current cancellation circuitry on their input stages. The LMP7731 has rail-to-rail input. This is achieved by having two input stages in parallel. Figure 1 shows only one of the input stages as the circuitry is symmetrical for both stages. Figure 1 shows that as the common mode voltage gets closer to one of the extreme ends, current I1 significantly increases. This increased current shows as an increase in voltage drop across resistor R1 equal to I1*R1 on IN+ of the amplifier. This voltage contributes to the offset voltage of the amplifier. When common mode voltage is in the mid-range, the transistors are operating in the linear region and I1 is significantly small. The voltage drop due to I1 across R1 can be ignored as it is orders of magnitude smaller than the amplifier's input offset voltage. As the common mode voltage gets closer to one of the rails, the offset voltage generated due to I1 increases and becomes comparable to the amplifiers offset voltage. 20175206 FIGURE 1. Input Bias Current Cancellation INPUT VOLTAGE NOISE MEASUREMENT The LMP7731 has very low input voltage noise. The peak-topeak input voltage noise of the LMP7731 can be measured using the test circuit shown in Figure 2 20175255 FIGURE 2. 0.1 Hz to 10 Hz Noise Test Circuit www.national.com 14 LMP7731 The frequency response of this noise test circuit at the 0.1 Hz corner is defined by only one zero. The test time for the 0.1 Hz to 10 Hz noise measurement using this configuration should not exceed 10 seconds, as this time limit acts as an additional zero to reduce or eliminate the noise contributions of noise from frequencies below 0.1 Hz. Figure 3 shows typical peak-to-peak noise for the LMP7731 measured with the circuit in Figure 2 for the LMP7731. During the peak-to-peak noise measurement, the LMP7731 must be shielded. This prevents offset variations due to airflow. Offset can vary by a few nV due to this airflow and that can invalidate measurements of input voltage noise with a magnitude which is in the same range. For similar reasons, sudden motions must also be restricted in the vicinity of the test area. The feed-through which results from this motion could increase the observed noise value which in turn would invalidate the measurement. DIODES BETWEEN THE INPUTS The LMP7731 has a set of anti-parallel diodes between the input pins as shown in Figure 5. These diodes are present to protect the input stage of the amplifier. At the same time, they limit the amount of differential input voltage that is allowed on the input pins. A differential signal larger than the voltage needed to turn on the diodes might cause damage to the diodes. The differential voltage between the input pins should be limited to ±3 diode drops or the input current needs to be limited to ±20 mA. 20175268 FIGURE 3. 0.1 Hz to 10 Hz Input Voltage Noise Measuring the very low peak-to-peak noise performance of the LMP7731, requires special testing attention. In order to achieve accurate results, the device should be warmed up for at least five minutes. This is so that the input offset voltage of the op amp settles to a value. During this warm up period, the offset can typically change by a few µV because the chip temperature increases by about 30°C. If the 10 seconds of the measurement is selected to include this warm up time, some of this temperature change might show up as the measured noise. Figure 4 shows the start-up drift of five typical LMP7731 units. 20175204 FIGURE 5. Anti-Parallel Diodes between Inputs 20175230 FIGURE 4. Start-Up Input Offset Voltage Drift 15 www.national.com LMP7731 DRIVING AN ADC Analog to Digital Converters, ADCs, usually have a sampling capacitor on their input. When the ADC's input is directly connected to the output of the amplifier a charging current flows from the amplifier to the ADC. This charging current causes a momentary glitch that can take some time to settle. There are different ways to minimize this effect. One way is to slow down the sampling rate. This method gives the amplifier sufficient time to stabilize its output. Another way to minimize the glitch caused by the switch capacitor is to have an external capacitor connected to the input of the ADC. This capacitor is chosen so that its value is much larger than the internal switching capacitor and it will hence provide the voltage needed to quickly and smoothly charge the ADC's sampling capacitor. Since this large capacitor will be loading the output of the amplifier as well, an isolation resistor is needed between the output of the amplifier and this capacitor. The isolation resistor, RISO, separates the additional load capacitance from the output of the amplifier and will also form a low-pass filter and can be designed to provide noise reduction as well as anti-aliasing. The drawback to having RISO is that it reduces signal swing since there is some voltage drop across it. Figure 6 (a) shows the ADC directly connected to the amplifier. To minimize the glitch in this setting, a slower sample rate needs to be used. Figure 6 (b) shows RISO and an external capacitor used to minimize the glitch. THERMOPILE AMPLIFIER Thermopile Sensors Thermopiles are arrays of interconnected thermocouples which can detect the surface temperature of an object through radiation rather than direct contact. The hot and cold junctions of the thermocouples are thermally isolated. The hot junctions are exposed to IR radiation emitted from the measurement surface and the cold junctions are connected to a heat sink. The incident IR changes the temperature of the hot junctions of the thermopile and produces an output voltage proportional to this change. The hot junction of the thermopile is covered with a highly emissive coating. The IR radiation incident to this highly emissive material changes the temperature of this coating. The temperature change is converted to a voltage by the thermopile. Emissivity represents the radiation or absorption efficiency of a material relative to a black body. An ideal black body has an emissivity of 1.0. Excluding shiny metals, most objects have emissivities above 0.85. As a practical matter, shiny metals are not good candidates for IR sensing because of their low emissivity. The low emissivity means that the material is highly reflective. Reflective materials often “reflect” the temperature of their surrounding environment rather than their own heat radiation. This makes them not suitable for thermopile applications. The output voltage of a thermopile is related to temperature and emissivity by the following formula: Where: VOUT : Output voltage of the thermopile K : Proportionality constant εOBJ: Emissivity of object being measured TOBJ: Temperature of object being measured δ : Correction factor. (This is needed since thermopile filters do not allow all wavelengths to enter the sensor.) εTP: Emissivity of the thermopile TTP: Temperature of the thermopile As mentioned above, the IR radiation generates a static voltage across the pyroelectric material. If the illumination is constant, the signal level detection declines. This is why the radiation needs to be periodically refreshed. This task is usually achieved by the means of a mechanical chopper in front of the detector. Thermopiles offer much faster response time compared to other temperature measurement devices. Packaged thermistors and thermocouples have response times that can range up to a few seconds, whereas packaged thermopiles can easily achieve response times in the order of tens of milliseconds. Thermopiles also provide superior thermal isolation compared to their contact temperature measurement counterparts. Physical contact disturbs the systems temperature and also creates temperature gradients. Figure 7 shows a simplified schematic of a thermopile. The cold junctions are connected to a heat sink, and the absorber material covers the hot junction. The output voltage resulting from the temperature difference between the two junctions is measured at the two ends of the array of thermocouples. As is evident in Figure 7, increasing the number of thermocouples in a thermopile increases the output voltage range. This also increases the active area of the thermopile sensor. 16 20175205 FIGURE 6. Driving an ADC www.national.com LMP7731 and 20175207 FIGURE 7. Thermopile Thermopiles have very wide temperature ranges of -100°C to 1000°C When choosing a thermopile for a certain application, one must pay attention to several parameters. Thermopiles' sensitivity, or responsivity, is determined by the ratio of output voltage to the absorbed input signal power and is usually specified in V/W. Typical sensitivity of thermopiles ranges from 10s of V/W to about 100 V/W. Generally, higher values of sensitivity are desirable. Sensitivity is dependent on the absorber's area and number of thermocouples used in the sensor. Sensitivity is often represented by S where: S = VOUT/PIN The sensitivity of a thermopile varies with change in temperature. This change is usually specified as the Temperature Coefficient, TC, of sensitivity. Lower numbers are desired for this parameter. Resistance of the thermopiles is usually specified in the datasheet. This is the impedance which will be seen by the input of the amplifier used to process the thermopile's output signal. Typical values for thermopile resistance, RTP, range from 10s of kilo-ohms to about 100 kΩ. This resistance is also a function of temperature. The temperature coefficient of the resistance is usually specified in a thermopile's datasheet. As with any other parameter, minimum variation with temperature is desired. The dominant noise source for a thermopile is its resistance. The noise spectral density of a resistor is calculated by: As shown above, the NEP of two thermopiles cannot be compared without considering the corresponding active areas. A better way to compare thermopiles is to look at their specific detectivity, D*. Specific detectivity includes both the device noise and its sensitivity. It is normalized with respect to the detector's active area and also noise bandwidth. D* is given by: The unit of D* is cm / W. Typical values for specific detectivity range from 108 to 3*108 cm / W. After receiving radiation, the thermopile takes some time before it comes to thermal equilibrium. The time it takes for the sensor to achieve this equilibrium is called response time or time constant of the sensor. Clearly, lower time constants are very desirable. Precision Amplifier Since the output of thermopiles is usually very small and at most in the order of only a few millivolts, the first part of the signal conditioning path should involve amplification. In choosing an amplifier for this purpose, a few different sensor characteristics and the way they interface with the amplifier should be considered. Sensor's Impedance and Op Amp's Input Bias Current: The input bias current causes a voltage drop across the sensor and the amount of this voltage is equal to the sensor's impedance multiplied by the magnitude of bias current. The higher the sensor's input impedance, the more accentuated the effect of the amplifier's input bias current will be. For very high impedance sensors, it is imperative that op amps with very low input bias currents be used. Thermopiles have input impedances in the range of 100 kΩ, so input bias current is not as critical as in some other applications. Sensor's Output Voltage Range: The output signal of the sensor is fed into the op amp where it will be amplified or otherwise conditioned, e.g. level shifted, buffered. It is important to pay attention to different parameters of this output signal. The lowest expected level of the sensor's output is very important. It is necessary to compare this level with the different parameters contributing to the amplifier's total input noise. If the sensor's output level is in the same order of magnitude or smaller than the op amp's total input noise, then signal integrity at the op amp's output and the ADC's input will be compromised. Where k is the Boltzman constant and T is absolute temperature. The unit of noise spectral density is: V/ For the thermopile sensor, this noise is usually represented by VNOISE where: A typical value for this voltage noise is in the order of a few . tens of nV/ The Noise Equivalent Power, NEP, is often used to specify the minimum detectable signal level per square root bandwidth. A smaller NEP is desired, however NEP is dependent on the thermopile active area, AD. For a thermopile 17 www.national.com LMP7731 20175260 FIGURE 8. Thermopile Amplifier Figure 8 shows the LMP7731 used as a thermopile amplifier. The LMP7731 is a great choice for use with thermopile sensors. The LMP7731 provides unprecedented accuracy and precision because of its very low input voltage noise and the very low 1/f corner frequency. The 1/f noise is one of the main sources of error in DC operating mode. Since thermopiles and most other sensors operate on DC signals, signal integrity at the DC level is very important. The LMP7731 also has very low offset voltage and offset voltage drift which greatly reduces the effects of input offset voltage of the amplifier on the thermopile signal. The thermopile used in this circuit is TPS332 from PerkinElmer Optoelectronics, PKI. This thermopile has an internal resistance, RTP, of 75 kΩ. The output voltage of the thermopile is represented with a DC voltage source. The TPS332 has a thermistor integrated in the package. The thermistor is used to measure the ambient temperature of the thermopile at the time of measurement. The thermistor's resistance at room temperature is 30 kΩ. More information about this thermopile and other sensors from PKI can be found on http://www.perkinelmer.com/ The circuit in Figure 8 shows how the LMP7731 is connected to the thermopile. This circuit is comprised of two LMP7731 amplifiers, the LM4140A-2.5 which is a precision voltage reference, the ADC122S021 which is a 2 channel Analog to Digital converter, and the thermopile sensor. Note that the two amplifiers used in this circuit are numbered for ease of reference. The LMP7731 amplifiers are referred to as amplifier 1 and amplifier 2 per Figure 8. In Figure 8 the LM4140A is providing a precision voltage reference of 2.5V. This reference voltage is applied to the thermistor via the 30 kΩ resistor. The thermistor's resistance is converted to a voltage using this set up. This voltage is fed into the ADC's channel one. The ADC uses this voltage and the thermistor's look up table to convert this voltage to temperature. The 2.5V reference is also fed into amplifier 1, which is configured as a buffer. This LMP7731 transfers the 2.5V signal to both inputs of amplifier 2. This means the 2.5V will show up on the output of amplifier 2. Having an output level that is mid-supply is important since the thermopile sensor has a bipolar output signal and this way the amplifier can accurately gain the thermopile voltage, whether its polarity is positive or negative. It is also important because the output signal of amplifier 2 is only positive. ADCs can only handle positive signals on their inputs. Amplifier 2 is used to gain and filter the thermopile signal. The low pass filter ensures that AC noise will not be gained up and as a result the output signal will be cleaner. The output of amplifier 2 is fed into the ADC's channel 0. The ADC uses the ambient temperature, which was calculated using the voltage on Channel 1 and the thermistor's look up table, along with the thermopiles' gained output voltage available on channel 0 and the thermopile's look up table to determine the object's temperature. www.national.com 18 LMP7731 Physical Dimensions inches (millimeters) unless otherwise noted 5-Pin SOT23 NS Package Number MF05A 19 www.national.com LMP7731, Low Noise, Precision, RRIO, Amplifier in SOT23–5 Notes THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION (“NATIONAL”) PRODUCTS. NATIONAL MAKES NO REPRESENTATIONS OR WARRANTIES WITH RESPECT TO THE ACCURACY OR COMPLETENESS OF THE CONTENTS OF THIS PUBLICATION AND RESERVES THE RIGHT TO MAKE CHANGES TO SPECIFICATIONS AND PRODUCT DESCRIPTIONS AT ANY TIME WITHOUT NOTICE. NO LICENSE, WHETHER EXPRESS, IMPLIED, ARISING BY ESTOPPEL OR OTHERWISE, TO ANY INTELLECTUAL PROPERTY RIGHTS IS GRANTED BY THIS DOCUMENT. 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