The
QD48T012033
dual
output
through-hole
mounted
DC-DC converter offers unprecedented performance in a quarter brick
package by providing two independently regulated high current
outputs. This is accomplished by the use of patent pending circuit and
packaging techniques to achieve ultra-high efficiency, excellent
thermal performance and a very low body profile.
In telecommunications applications the QD48 converters provide up
to 15 A per channel simultaneously – 30 A total – with thermal
performance far exceeding existing dual quarter bricks and
comparable to dual half-bricks. Low body profile and the preclusion of
heat sinks minimize airflow shadowing, thus enhancing cooling for
downstream devices. The use of 100% surface-mount technologies
for assembly, coupled with Power Bel Solutions advanced electric and
thermal circuitry and packaging, results in a product with extremely
high quality and reliability.
RoHS lead-free solder and lead-solder-exempted products are
available
Delivers up to 15 A simultaneously on 1.2 VDC and 3.3 VDC outputs
Can replace two single output quarter-bricks
Minimal cross-channel interference
High efficiency: 85.5% @ 2x15 A, 86% @ 2x7.5 A
Starts-up into pre-biased output
No minimum load required
No heat sink required
Low profile: 0.28” [7.2 mm]
Low weight: 1 oz [28 g] typical
Industry-standard footprint: 1.45” x 2.30”
Industry-standard pinout
Meets Basic Insulation Requirements of EN60950
Withstands 100 V input transient for 100 ms
On-board LC input filter
Fixed-frequency operation
Fully protected
Output voltage trim range: ±10% for both outputs
Trim resistor via industry-standard equations
High reliability: MTBF 2.6 million hours, calculated per Telcordia TR332, Method I Case 1
Positive or negative logic ON/OFF option
Approved to the latest edition and amendment of ITE Safety standards,
UL/CSA 60950-1 and IEC60950-1
Meets conducted emissions requirements of FCC Class B and
EN55022 Class B with external filter
All materials meet UL94, V-0 flammability rating
QD48T012033
2
Conditions: TA = 25ºC, Airflow = 300 LFM (1.5 m/s), Vin = 48 VDC, unless otherwise specified.
PARAMETER
Absolute Maximum Ratings
CONDITIONS / DESCRIPTION
Input Voltage
Continuous
MIN
TYP
MAX
UNITS
0
80
VDC
Operating Ambient Temperature
-40
85
°C
Storage Temperature
-55
125
°C
Input Characteristics
Operating Input Voltage Range
Input Under Voltage Lockout
36
48
75
VDC
33
34
35
VDC
31
32
Non-latching
Turn-on Threshold
Turn-off Threshold
Input Transient Withstand (Susceptibility)
33
VDC
100
VDC
10,000
10,000
μF
μF
15
15
ADC
ADC
18
18
19.5
19.5
ADC
ADC
20
20
30
30
A
A
4
4
Arms
Arms
100 ms
Output Characteristics
External Load Capacitance
1.2 V
3.3 V
Output Current Range
1.2 V
3.3 V
Current Limit Inception
1.2 V
3.3 V
Peak Short-Circuit Current
1.2 V
3.3 V
RMS Short-Circuit Current
1.2 V
3.3 V
Plus full load (resistive)
Plus full load (resistive)
At nominal output voltage 1.2 V
At nominal output voltage 3.3 V
Non-latching
Non-latching
0
0
15.75
15.75
Non-latching. Short=10mΩ.
Non-latching. Short=10mΩ.
Non-latching
Non-latching
Isolation Characteristics
I/O Isolation
2000
Isolation Capacitance
VDC
ρF
1.3
Isolation Resistance
10
MΩ
Feature Characteristics
Switching Frequency
Output Voltage Trim Range1
1.2 V
3.3 V
Output Over-Voltage Protection
1.2 V
3.3 V
435
See section: Output Voltage Adjust/TRIM
Simultaneous with 1.2 V output
-10
-10
Non-latching
Non-latching
1.4
3.85
1.48
4.125
kHz
+10
+10
%
%
1.56
4.25
V
V
Over-Temperature Shutdown (PCB)
Non-latching
120
°C
Auto-Restart Period
Applies to all protection features
100
ms
3
ms
Turn-On Time
3.3 V 1.2 V tracks 3.3 V
ON/OFF Control (Positive Logic)
Converter Off
-20
0.8
VDC
Converter On
2.4
20
VDC
ON/OFF Control (Negative Logic)
Converter Off
2.4
20
VDC
Converter On
-20
0.8
VDC
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QD48T012033
3
Input Characteristics
Maximum Input Current
1.2 VDC @ 15 ADC, 3.3 VDC @ 15 ADC,
Vin = 36 V
Input Stand-by Current
Vin = 48 V, converter disabled
2.6
Input No Load Current (0 load on the output)
Vin = 48 V, converter enabled
53
mAdc
Input Reflected-Ripple Current
See Figure 32 - 25MHz bandwidth
6
mAPK-PK
Input Voltage Ripple Rejection
120Hz
TBD
dB
2.2
ADC
mAdc
Output Characteristics
Output Voltage Set Point2 (no load)
1.2 V
3.3 V
-40ºC to 85ºC
-40ºC to 85ºC
1.193
3.272
1.205
3.305
1.217
3.338
VDC
VDC
Output Regulation
Over Line
1.2 V
3.3 V
Over Load3
1.2 V
3.3 V
Cross Regulation4
1.2 V
3.3 V
Output Voltage Range
1.2 V
3.3 V
For Iout2 (3.3 V) change from 0 to 15 A
For Iout1 (1.2 V) change from 0 to 15 A
Over line, load and cross regulation
Over line, load and cross regulation
Output Ripple and Noise - 25MHz bandwidth
1.2 V
3.3 V
Full load + 1 μF ceramic
Full load + 1 μF ceramic
±2
±2
mV
mV
-10
-10
mV
mV
-5
-5
mV
mV
1.176
3.234
20
25
1.224
3.366
VDC
VDC
30
40
mVPK-PK
mVPK-PK
Dynamic Response
Load Change: 50% to 75% to 50%
di/dt = 0.1 A/μS
1.2 V
3.3 V
ΔIout = 25% of IoutMax
Co = 10 μF tant. + 1 μF ceramic (Fig.19)
Co = 10 μF tant. + 1 μF ceramic (Fig.20)
Setting Time to 1%
1.2 V
3.3 V
75
50
mV
mV
100
100
µs
µs
100
100
mV
mV
60
60
µs
µs
85.5
%
86
%
di/dt = 5 A/μS
Co = 300 μF tant. + 1 μF ceramic (Fig.21)
Co = 300 μF tant. + 1 μF ceramic (Fig.22)
1.2 V
3.3 V
Setting Time to 1%
1.2 V
3.3 V
Efficiency
1.2 V 100% Load, 3.3 V 100% Load
1.2 V 50% Load, 3.3 V 50% Load
1)
2)
3)
4)
Vout1 and Vout2 can be simultaneously increased or decreased up to 10% via the Trim function. When trimming up, in order
not to exceed the converter‘s maximum allowable output power capability equal to the product of the nominal output voltage
and the allowable output current for the given conditions, the designer must, if necessary, decrease the maximum current
(originally obtained from the derating curves) by the same percentage to ensure the converter’s actual output power remains
at or below the maximum allowable output power.
No load set point is 5 mV higher than the nominal voltage, to partially compensate voltage drop on the output pins and
traces to the load.
Load regulation is affected with resistance of the output pins (approximately 0.3 mΩ) since there is no remote sense.
Cross regulation is affected with resistance of the RETURN pin (approximately 0.3 mΩ) since there is no remote sense.
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QD48T012033
4
These power converters have been designed to be stable with no external capacitors when used in low inductance input
and output circuits.
However, in many applications, the inductance associated with the distribution from the power source to the input of the
converter can affect the stability of the converter. The addition of a 33 µF electrolytic capacitor with an ESR < 1 across
the input helps ensure stability of the converter. In many applications, the user has to use decoupling capacitance at the
load. The converter will exhibit stable operation with external load capacitance up to 10,000 µF on both outputs.
The ON/OFF pin is used to turn the power converter on or off remotely via a system signal. There are two remote control
options available, positive logic and negative logic and both are referenced to Vin(-). Typical connections are shown in
Fig. 1.
Q
TM
Vin (+)
Family
Converter
(Top View)
Vout2 (+)
Rload2
TRIM
ON/OFF
Vin
RTN
Rload1
Vin (-)
Vout1 (+)
CONTROL
INPUT
Figure 1. Circuit configuration for ON/OFF function.
The positive logic version turns on when the ON/OFF pin is at logic high and turns off when at logic low. The converter is on
when the ON/OFF pin is left open.
The negative logic version turns on when the pin is at logic low and turns off when the pin is at logic high. The ON/OFF pin
can be hard wired directly to Vin(-) to enable automatic power up of the converter without the need of an external control
signal.
ON/OFF pin is internally pulled-up to 5 V through a resistor. A mechanical switch, open collector transistor, or FET can be
used to drive the input of the ON/OFF pin. The device must be capable of sinking up to 0.2 mA at a low level voltage of
0.8 V. An external voltage source of ±20 V max. may be connected directly to the ON/OFF input, in which case it should be
capable of sourcing or sinking up to 1 mA depending on the signal polarity. See the Start-up Information section for system
timing waveforms associated with use of the ON/OFF pin.
The converter’s output voltages can be adjusted simultaneously up 10% or down 10% relative to the rated output voltages
by the addition of an externally connected resistor. For output voltage 3.3 V, trim up to 10% is guaranteed only at Vin ≥ 40
V, and it is marginal (8% to 10%) at Vin = 36 V.
The TRIM pin should be left open if trimming is not being used. To minimize noise pickup, a 0.1 µF capacitor is connected
internally between the TRIM and RETURN pins.
Q Family
Converter
Vout2 (+)
(Top View)
TRIM
TM
Vin (+)
Vin
R T-INCR
Rload2
ON/OFF
RTN
Rload1
Vin (-)
Vout1 (+)
Figure 2. Configuration for increasing output voltage.
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QD48T012033
5
To increase the output voltage (refer to Fig. 2), a trim resistor, RT-INCR, should be connected between the TRIM (Pin 6) and
RETURN (Pin 5), with a value from the table below.
Q Family
Converter
Vout2 (+)
(Top View)
TRIM
TM
Vin (+)
Rload2
R T-DECR
ON/OFF
Vin
RTN
Rload1
Vin (-)
Vout1 (+)
Figure 3. Configuration for decreasing output voltage.
To decrease the output voltage, a trim resistor RT-DECR, (Fig. 3) should be connected between the TRIM (Pin 6) and Vout2(+)
pin (Pin 7), with a value from the table below, where:
Δ = percentage of increase or decrease Vout(NOM).
Note 1: Both outputs are trimmed up or down simultaneously.
Note 1:
Both outputs are trimmed up or down simultaneously.
TRIM RESISTOR
(VOUT INCREASE)
TRIM RESISTOR
(VOUT DECREASE)
Δ [%]
RT-INCR [kΩ]
Δ [%]
RT-DECR [kΩ]
1
54.9
-1
68.1
2
24.9
-2
30.1
3
14.3
-3
17.8
4
9.31
-4
11.5
5
6.34
-5
7.68
6
4.32
-6
5.36
7
2.80
-7
3.48
8
1.69
-8
2.10
9
0.825
-9
1.05
10
0
-10
0
Note 2: The above trim resistor values match those typically used in industry-standard dual quarter bricks.
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6
QD48T012033
Input under-voltage lockout is standard with this converter. The converter will shut down when the input voltage drops below
a pre-determined voltage.
The input voltage must be at least 35 V for the converter to turn on. Once the converter has been turned on, it will shut off
when the input voltage drops below 31 V. This feature is beneficial in preventing deep discharging of batteries used in
telecom applications.
The converter is protected against overcurrent or short circuit conditions on both outputs. Upon sensing an over-current
condition, the converter will switch to constant current operation and thereby begin to reduce output voltages. If, due to
current limit, the output voltage Vout2 (3.3 V) drops below Vout1 - 0.6 V, converter will shut down. If, due to current limit, the
output voltage Vout1 (1.2 V) drops below 60% of its nominal value (0.7 V) the converter will shut down (Figs. 25 and 26).
Thus, current limit on one output does not affect regulation on the other output.
Once the converter has shut down, it will attempt to restart nominally every 100 ms with a typical 2% duty cycle (Figs. 27
and 29). The attempted restart will continue indefinitely until the overload or short circuit conditions are removed or the
output voltage rises above under-voltage threshold.
The converter will shut down if the output voltage across either Vout1(+) (Pin 4) or Vout2(+) (Pin 7) and RETURN (Pin 5)
exceeds the threshold of the OVP circuitry. The OVP protection is separate for Vout1 and Vout2 with their own reference
independent of the output voltage regulation loops. Once the converter has shut down, it will attempt to restart every 100
ms until the OVP condition is removed.
The converter will shut down under an over temperature condition to protect itself from overheating caused by operation
outside the thermal derating curves, or operation in abnormal conditions such as system fan failure. After the converter has
cooled to a safe operating temperature, it will automatically restart.
The converters meet North American and International safety regulatory requirements per UL60950 and EN60950. Basic
Insulation is provided between input and output.
To comply with safety agencies requirements, an input line fuse must be used external to the converter. A 4-A fuse is
recommended for use with this product.
EMC requirements must be met at the end-product system level, as no specific standards dedicated to EMC characteristics
of board mounted component dc-dc converters exist. However, Power Bel Solutions tests its converters to several system
level standards, primary of which is the more stringent EN55022, Information technology equipment - Radio disturbance
characteristics - Limits and methods of measurement.
With the addition of a simple external filter (see application notes), all versions of the QD48T converters pass the requirements
of Class B conducted emissions per EN55022 and FCC, and meet at a minimum, Class A radiated emissions per EN 55022
and Class B per FCC Title 47CFR, Part 15-J. Please contact Power Bel Solutions Applications Engineering for details of this
testing.
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QD48T012033
7
VIN
Scenario #1: Initial Startup From Bulk Supply
ON/OFF function enabled, converter started via application of
VIN. See Figure 4.
Time
t0
t1
t2
t3
Comments
ON/OFF pin is ON; system front-end power is
toggled on, VIN to converter begins to rise.
VIN crosses Under-Voltage Lockout protection circuit
threshold; converter enabled.
Converter begins to respond to turn-on command
(converter turn-on delay).
Output voltage VOUT1 reaches 100% of nominal value
ON/OFF
STATE
OFF
ON
VOUT2
VOUT2
VOUT1
t4
Output voltage VOUT2 reaches 100% of nominal
value.
For this example, the total converter startup time (t4- t1) is
typically 3 ms.
VOUT1
t0
t1 t2
t3
t
t4
Figure 4. Start-up scenario #1.
Scenario #2: Initial Startup Using ON/OFF Pin
With VIN previously powered, converter started via ON/OFF pin.
See Figure 5.
Time
t0
t1
Comments
VINPUT at nominal value.
Arbitrary time when ON/OFF pin is enabled (converter
enabled).
t2
End of converter turn-on delay.
t3
Output voltage VOUT1 reaches 100% of nominal value.
t4
Output voltage VOUT2 reaches 100% of nominal value.
For this example, the total converter startup time (t4- t1) is
typically 3 ms.
VIN
ON/OFF
STATE OFF
ON
VOUT2
VOUT2
VOUT1
VOUT1
t0
t1 t2
t3
t
t4
Figure 5. Startup scenario #2.
Scenario #3: Turn-off and Restart Using ON/OFF Pin
With VIN previously powered, converter is disabled and then
enabled via ON/OFF pin. See Figure 6.
VIN
Time
t0
t1
Comments
VIN and VOUT are at nominal values; ON/OFF pin ON.
ON/OFF pin arbitrarily disabled; converter output falls
to zero; turn-on inhibit delay period (100 ms typical) is
initiated, and ON/OFF pin action is internally inhibited.
t2
ON/OFF pin is externally re-enabled.
If (t2- t1) ≤ 100 ms, external action of ON/OFF
pin is locked out by startup inhibit timer.
If (t2- t1) > 100 ms, ON/OFF pin action is
internally enabled.
t3
Turn-on inhibit delay period ends. If ON/OFF pin is
ON, converter begins turn-on; if off, converter awaits
ON/OFF pin ON signal; see Figure 5.
t4
End of converter turn-on delay.
t5
Output voltage VOUT1 reaches 100% of nominal value.
t6
Output voltage VOUT2 reaches 100% of nominal value.
For the condition, (t2- t1) ≤ 100 ms, the total converter startup time
(t6- t2) is typically 103 ms. For (t2- t1) > 100 ms, startup will be
typically 3 ms after release of ON/OFF pin.
100 ms
ON/OFF
STATE OFF
ON
VOUT2
VOUT2
VOUT1
VOUT1
t0
t1
t2
t3 t4
t5 t6
t
Figure 6. Startup scenario #3.
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QD48T012033
8
The converter has been characterized for many operational aspects, to include thermal derating (maximum load current as
a function of ambient temperature and airflow) for vertical and horizontal mounting, efficiency, start-up and shutdown
parameters, output ripple and noise, transient response to load step-change, overload and short circuit.
The following pages contain specific plots or waveforms associated with the converter. Additional comments for specific
data are provided below.
All data presented were taken with the converter soldered to a test board, specifically a 0.060” thick printed wiring board
(PWB) with four layers. The top and bottom layers were not metalized. The two inner layers, comprising two-ounce copper,
were used to provide traces for connectivity to the converter.
The lack of metalization on the outer layers as well as the limited thermal connection ensured that heat transfer from the
converter to the PWB was minimized. This provides a worst-case but consistent scenario for thermal derating purposes.
All measurements requiring airflow were made in Power Bel Solutions vertical and horizontal wind tunnel facilities using
infrared (IR) thermography and thermocouples for thermometry.
Ensuring that the components on the converter do not exceed their ratings is important to maintaining high reliability. If one
anticipates operating the converter at or close to the maximum loads specified in the derating curves, it is prudent to check
actual operating temperatures in the application. Thermographic imaging is preferable; if this capability is not available, then
thermocouples may be used. Power Bel Solutions recommends the use of AWG #40 gauge thermocouples to ensure
measurement accuracy. Careful routing of the thermocouple leads will further minimize measurement error. Refer to Figure
33 for optimum measuring thermocouple location.
Available output power and load current vs. ambient temperature and airflow rates are given in Figs. 7-10. Ambient
temperature was varied between 25°C and 85°C, with airflow rates from 30 to 500 LFM (0.15 to 2.5 m/s), and vertical and
horizontal converter mounting.
For each set of conditions, the maximum load current was defined as the lowest of:
(i)
(ii)
The output current at which either any FET junction temperature did not exceed a maximum specified temperature
(120°C) as indicated by the thermographic image, or
The nominal rating of the converter (15 A on either output)
During normal operation, derating curves with maximum FET temperature less than or equal to 120°C should not be
exceeded. Temperature on the PCB at the thermocouple location shown in Fig. 33 should not exceed 118°C in order to
operate inside the derating curves.
Efficiency vs. load current plots are shown in Figs. 11-16 for ambient temperature of 25ºC, airflow rate of 300 LFM (1.5 m/s),
both vertical and horizontal orientations, and input voltages of 36 V, 48 V and 72 V, for different combinations of the loads
on outputs Vout1 and Vout2.
Output voltage waveforms during the turn-on transient using the ON/OFF pin, are shown without and with full rated load
currents (resistive load) in Figs. 17 and 18, respectively.
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QD48T012033
9
100
100
90
90
80
80
Total Output Power [W]
Total Output Power [W]
Figure 29 shows the output voltage ripple waveform, measured at full rated load current on both outputs with a 1 µF ceramic
capacitor across both outputs. Note that all output voltage waveforms are measured across a 1 F ceramic capacitor.
The input reflected ripple current waveforms are obtained using the test setup shown in Fig. 30. The corresponding
waveforms are shown in Figs. 31 and 32.
70
60
50
500 LFM (2.5 m/s)
400 LFM (2.0 m/s)
300 LFM (1.5 m/s)
200 LFM (1.0 m/s)
100 LFM (0.5 m/s)
30 LFM (0.15 m/s)
40
30
20
70
60
50
500 LFM (2.5 m/s)
400 LFM (2.0 m/s)
300 LFM (1.5 m/s)
200 LFM (1.0 m/s)
100 LFM (0.5 m/s)
30 LFM (0.15 m/s)
40
30
20
10
10
0
20
30
40
50
60
70
80
0
20
90
30
50
60
70
80
90
Ambient Temperature [°C]
Ambient Temperature [°C]
Figure 7. Available output power for balanced load current
(Iout1 = Iout2) vs. ambient air temperature and airflow rates for
converter mounted vertically with Vin = 48 V, air flowing from
pin 3 to pin 1 and maximum FET temperature 120 C.
Figure 8. Available output power for balanced load current
(Iout1 = Iout2) vs. ambient air temperature and airflow rates for
converter mounted horizontally with Vin = 48 V, air flowing
from pin 3 to pin 4 and maximum FET temperature 120 C.
20.0
20.0
17.5
Load Current Iout1, Iout2 [Adc]
Load Current Iout1, Iout2 [Adc]
40
15.0
12.5
10.0
500 LFM (2.5 m/s)
400 LFM (2.0 m/s)
300 LFM (1.5 m/s)
200 LFM (1.0 m/s)
100 LFM (0.5 m/s)
30 LFM (0.15 m/s)
7.5
5.0
2.5
0.0
17.5
15.0
12.5
10.0
500 LFM (2.5 m/s)
400 LFM (2.0 m/s)
300 LFM (1.5 m/s)
200 LFM (1.0 m/s)
100 LFM (0.5 m/s)
30 LFM (0.15 m/s)
7.5
5.0
2.5
0.0
20
30
40
50
60
70
80
90
20
30
Ambient Temperature [°C]
40
50
60
70
80
90
Ambient Temperature [°C]
Figure 9. Available balanced load current (Iout1 = Iout2) vs.
ambient air temperature and airflow rates for converter
mounted vertically with Vin = 48 V, air flowing from pin 3 to pin
1 and maximum FET temperature 120 C.
Figure 10. Available balanced load current (Iout1 = Iout2) vs.
ambient temperature and airflow rates for converter mounted
horizontally with Vin = 48 V, air flowing from pin 3 to pin 4 and
maximum FET temperature 120 C.
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QD48T012033
0.95
0.95
0.90
0.90
0.85
0.85
Efficiency
Efficiency
10
0.80
72 V
48 V
36 V
0.75
0.80
72 V
48 V
36 V
0.75
0.70
0.70
Iout2 = 7.5 Adc
Iout2 = 7.5 Adc
0.65
0.65
0
2
4
6
8
14
12
10
16
0
2
6
4
Load Current Iout1 [Adc]
Figure 11. Efficiency vs. load current Iout1 and input voltage
for converter mounted vertically with air flowing from pin 3 to
pin 1 at a rate of 300 LFM (1.5 m/s), for Iout2 = 7.5 A and
C.
0.95
0.95
0.90
0.90
0.85
0.85
0.80
72 V
48 V
36 V
0.75
14
16
0.80
72 V
48 V
36 V
0.75
0.70
0.70
Iout1 = 7.5 Adc
Iout1 = 7.5 Adc
0.65
0.65
0
2
4
6
8
10
12
14
16
0
2
4
6
Load Current Iout2 [Adc]
8
10
12
14
16
Load Current Iout2 [Adc]
Figure 13. Efficiency vs. load current Iout2 and input voltage
for converter mounted vertically with air flowing from pin 3 to
pin 1 at a rate of 300 LFM (1.5 m/s), for Iout1 = 7.5 A and
C.
Figure 14. Efficiency vs. load current Iout2 and input voltage
for converter mounted horizontally with air flowing from pin 3
to pin 4 at a rate of 300 LFM (1.5 m/s), for Iout1 = 7.5 A and
Ta
0.95
0.95
0.90
0.90
0.85
0.85
Efficiency
Efficiency
12
10
Figure 12. Efficiency vs. load current Iout1 and input voltage
for converter mounted horizontally with air flowing from pin 3
to pin 4 at a rate of 300 LFM (1.5 m/s), for Iout2 = 7.5 A and
C.
Efficiency
Efficiency
8
Load Current Iout1 [Adc]
0.80
72 V
48 V
36 V
0.75
0.80
72 V
48 V
36 V
0.75
0.70
0.70
0.65
0.65
0
2
4
6
8
10
12
14
16
Load Current Iout1 = Iout2 [Adc]
Figure 15. Efficiency vs. balanced load current (Iout1 = Iout2)
and input voltage for converter mounted vertically with air
flowing from pin 3 to pin 1 at a rate of 300 LFM (1.5 m/s) and
C.
0
2
4
6
8
10
12
14
16
Load Current Iout1 = Iout2 [Adc]
Figure 16. Efficiency vs. balanced load current (Iout1 = Iout2)
and input voltage for converter mounted horizontally with air
flowing from pin 3 to pin 4 at a rate of 300 LFM (1.5 m/s) and
C.
tech.support@psbel.com
QD48T012033
11
Figure 17. Turn-on transient waveforms at no load current and
Vin = 48 V, triggered via ON/OFF pin. Top trace: ON/OFF
signal (5 V/div.). Bottom traces: Vout1 (blue, 1 V/div.), Vout2
(red, 1 V/div.). Time scale: 1 ms/div.
Figure 18. Turn-on transient waveforms at full rated load
current (resistive) and Vin = 48 V, triggered via ON/OFF pin.
Top trace: ON/OFF signal (5 V/div.). Bottom traces: Vout1
(blue, 1 V/div.), Vout2 (red, 1 V/div.). Time scale: 1 ms/div.
Figure 19. Output voltage response to Iout1 load current stepchange of 3.75 A (50%-75%-50%) at Iout2 = 7.5 A and Vin =
48 V. Ch1 = Vout1 (50 mV/div), Ch2 = Vout2 (50 mV/div), Ch3 =
Iout1 (10 A/div.), Ch4 = Iout2 (10 A/div.). Current slew rate: 0.1
A/µs, Co = 10 µF tantalum + 1 µF ceramic. Time scale: 0.5
ms/div.
Figure 20. Output voltage response to Iout2 load current stepchange of 3.75 A (50%-75%-50%) at Iout1 = 7.5 A and Vin =
48 V. Ch1 = Vout1 (50 mV/div), Ch2 = Vout2 (50 mV/div), Ch3 =
Iout1 (10 A/div.), Ch4 = Iout2 (10 A/div.). Current slew rate: 0.1
A/µs, Co = 10 µF tantalum + 1 µF ceramic. Time scale: 0.5
Figure 21. Output voltage response to Iout1 load current stepchange of 3.75 A (50%-75%-50%) at Iout2 = 7.5 A and Vin = 48 V.
Ch1 = Vout1 (100 mV/div), Ch2 = Vout2 (100 mV/div), Ch3 = Iout1
(10 A/div.), Ch4 = Iout2 (10 A/div.). Current slew rate: 5 A/µs, Co =
300 µF tantalum + 1 µF ceramic. Time scale: 0.5 ms/div.
Figure 22. Output voltage response to Iout2 load current stepchange of 3.75 A (50%-75%-50%) at Iout1 = 7.5 A and Vin = 48 V.
Ch1 = Vout1 (100 mV/div), Ch2 = Vout2 (100 mV/div), Ch3 = Iout1
(10 A/div.), Ch4 = Iout2 (10 A/div.). Current slew rate: 5 A/µs, Co =
300 µF tantalum + 1 µF ceramic. Time scale: 0.5 ms/div.
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QD48T012033
12
Figure 23. Output voltage response to both Iout1 and Iout2 (out of
phase) load current step-change of 3.75 A (50%-75%-50%) at Vin
= 48 V. Ch1 = Vout1 (50 mV/div), Ch2 = Vout2 (50 mV/div), Ch3 =
Iout1 (10 A/div.), Ch4 = Iout2 (10 A/div.). Current slew rate: 0.1
A/µs, Co = 10 µF tantalum + 1 µF ceramic. Time scale: 1.0 ms/div.
Figure 24. Output voltage response to both Iout1 and Iout2 (out of
phase) load current step-change of 3.75 A (50%-75%-50%) at Vin
= 48 V. Ch1 = Vout1 (100 mV/div), Ch2 = Vout2 (100 mV/div), Ch3
= Iout1 (10 A/div.), Ch4 = Iout2 (10 A/div.). Current slew rate: 5
A/µs, Co = 300 µF tantalum + 1 µF ceramic. Time scale: 1.0
ms/div.
Note: The only cross-talk during transient is due to the common
RETURN pin for both outputs.
4.0
4.0
3.0
3.0
Vout [Vdc]
Vout [Vdc]
Vout2
2.0
Vout1
2.0
1.0
1.0
0
0
0
5
10
15
20
0
5
Figure 25. Output voltage Vout1 vs. load current Iout1 showing
current limit point and converter shutdown point. When Vout1
is in current limit, Vout2 is not affected until Vout1 reaches the
shut-down threshold of 60% of its nominal value. Input voltage
has almost no effect on Vout1 current limit characteristic.
15
20
Figure 26. Output voltage Vout2 vs. load current Iout2 showing
current limit point and converter shutdown point. When Vout2
is in current limit, Vout1 is not affected until Vout2 reaches the
shut-down threshold equal to Vout1 - 0.6 V. Input voltage has
almost no effect onVout1 current limit characteristic.
iS
10 H
source
inductance
Vsource
Figure 27. Output voltage ripple at full rated load current into a
resistive load on both outputs with Co = 1uF (ceramic) and Vin
= 48 V. Ch2 = Vout2, Ch1 = Vout1 (both 20 mV/div). Time
10
Iout [Adc]
Iout [Adc]
iC
33 F
ESR
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