Rev.2.3_00
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM
CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
The S-8333 Series is a CMOS step-up switching regulator which mainly consists of a reference voltage
circuit, an oscillator, an error amplifier, a PWM controller, an under voltage lockout circuit (UVLO), and a
timer latch short-circuit protection circuit. Because its minimum operating voltage is as low as 1.8 V, this
switching regulator is ideal for the power supply of an LCD or for portable systems that operate on a low
voltage. The internal oscillation frequency can be set up to 1.133 MHz, via the resistor connected to the
ROSC pin.
The maximum duty ratio of PWM control can be controlled by the resistor connected to the RDuty pin. The
soft-start function at power application is accomplished by combining the reference voltage control and
maximum duty control methods. Even if the voltage of the FB pin is retained lower than the reference
voltage due to the factor outside the IC, the output voltage is raised by controlling the maximum duty. The
phase compensation and gain value can be adjusted according to the values of the resistor and capacitor
connected to the CC pin. Therefore, the operation stability and transient response can be correctly set for
each application. The reference voltage accuracy is as high as 1.0 V ±1.5%, and any voltage can be
output by using an external output voltage setting resistor.
In addition, the delay time of the short-circuit protection circuit can be set by using the capacitor
connected to the CSP pin. If the maximum duty condition continues because of short-circuiting, the
capacitor externally connected to the CSP pin is charged, and oscillation stops after a specific time. The
short-circuit protection function is cancelled when the power supply is raised to the UVLO release voltage
after it has been lowered to the UVLO detection voltage. A ceramic capacitor or a tantalum capacitor is
used as the output capacitor, depending on the setting. This controller IC allows various settings and
selections and employs a small package, making it very easy to use.
Features
• Low voltage operation:
• Oscillation frequency:
• Maximum duty:
•
•
•
•
•
•
•
•
1.8 V to 6.0 V
286 kHz to 1.133 MHz (selectable by external resistor)
Settable up to 88.5% by external resistor
47 to 88.5% (oscillation frequency; 500 kHz or more)
47 to 80% (oscillation frequency; less than 500 kHz)
Reference voltage:
1.0 V ±1.5%
Range of operation temperature: −40 to +85°C
UVLO (under-voltage lockout) function:
Detection voltage can be selected from between 1.5 V and 2.3 V in 0.1 V step.
Hysteresis width can be selected from between 0.1 V and 0.3 V in 0.1 V step.
Timer latch short-circuit protection circuit:
Delay time can be set using an external capacitor.
Soft-start function:
Soft-start time can be selected in three steps, 10 ms, 15 ms, and 20 ms.
Both reference voltage control and maximum duty control methods are applied
Phase compensation external setting:
Control is possible via the resistor connected between the CC and GND pins
and capacitor
Small package:
SNT-8A, 8-Pin TSSOP
Lead-free products
Applications
• Power supplies for LCDs and CCDs
• Power supplies for portable equipment
Packages
Package Name
SNT-8A
8-Pin TSSOP
Drawing Code
Package
Tape
Reel
Land
PH008-A
FT008-A
PH008-A
FT008-E
PH008-A
FT008-E
PH008-A
Seiko Instruments Inc.
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STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
Block Diagram
VOUT
SD
L
RDuty
VIN
UVLO
M1
CIN
ROSC
+
PWM −
comparator
Timer latch
short-circuit
protection circuit
EXT
VSS
CSP
+
Error amplifier
−
Reference voltage
(1.0 V) soft-start
circuit
CC
RZ CZ
Figure 1 Block Diagram
2
CFB RFB1
Oscillator
Maximum duty
soft-start circuit
Seiko Instruments Inc.
CL
FB
RFB2
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
Product Name Structure
1. Product name
S-8333
A
x
x
x
- xxxx
G
Package name(abbreviation) and packing specifications
I8T1: SNT-8A, Tape
T8T1: 8-Pin TSSOP, Tape
Soft-start time setting
A: 10 ms
B: 15 ms
C: 20 ms
UVLO setting
A: 2.3 V
B: 2.2 V
C: 2.1 V
D: 2.0 V
E: 1.9 V
F: 1.8 V
G: 1.7 V
H: 1.6 V
I: 1.5 V
UVLO hysteresis setting
A: 0.1 V
B: 0.2 V
C: 0.3 V
Seiko Instruments Inc.
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STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
Pin Configurations
Table 1
SNT-8A
Top view
Pin No.
Symbol
Description
1
CC
Error amplifier circuit output phase
compensation pin
Output voltage feedback pin
1
8
2
FB
2
7
3
CSP
Short-circuit protection delay time setting pin
3
6
4
VIN
Power supply input pin
5
5
EXT
External transistor connection pin
6
VSS
GND pin
7
ROSC
Oscillation frequency setting resistor
connection pin
8
RDuty
Maximum duty setting resistor connection pin
4
Figure 2
Table 2
8-Pin TSSOP
Top view
8
7
6
5
1
2
3
4
Figure 3
4
Pin No.
Symbol
Description
1
CC
Error amplifier circuit output phase
compensation pin
2
FB
Output voltage feedback pin
3
CSP
Short-circuit protection delay time setting pin
4
VIN
Power supply input pin
5
EXT
External transistor connection pin
6
VSS
GND pin
7
ROSC
Oscillation frequency setting resistor
connection pin
8
RDuty
Maximum duty setting resistor connection pin
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S-8333 Series
Absolute Maximum Ratings
Table 3 Absolute Maximum Ratings
(Unless otherwise specified: Ta = 25°C, VSS = 0 V)
Parameter
VIN pin voltage
FB pin voltage
EXT pin voltage
CSP pin voltage
CC pin voltage
CC pin current
ROSC pin voltage
ROSC pin current
RDuty pin voltage
RDuty pin current
SNT-8A
Power dissipation
8-Pin TSSOP
Symbol
VIN
VFB
VEXT
VCSP
VCC
ICC
VROSC
IROSC
VRDuty
IRDuty
PD
Operating ambient temperature
Storage temperature
Topr
Tstg
Ratings
VSS − 0.3 to VSS + 6.5
VSS − 0.3 to VSS + 6.5
VSS − 0.3 to VIN + 0.3
VSS − 0.3 to VIN + 0.3
VSS − 0.3 to VIN + 0.3
±10
VSS − 0.3 to VIN + 0.3
±10
VSS − 0.3 to VIN + 0.3
±10
450*1
300 (When not mounted on board)
700*1
−40 to +85
−40 to +125
Unit
V
V
V
V
V
mA
V
mA
V
mA
mW
mW
mW
°C
°C
*1. When mounted on board
[Mounted board]
(1) Board size:
(2) Name:
The absolute maximum ratings are rated values exceeding which the product could suffer
physical damage. These values must therefore not be exceeded under any conditions.
800
Power dissipation (PD) [mW]
Caution
114.3 mm × 76.2 mm × t1.6 mm
JEDEC STANDARD51-7
600
8-Pin TSSOP
SNT-8A
400
200
0
0
50
100
150
Ambient temperature (Ta) [°C]
Figure 4 Power Dissipation of Package (When mounted on board)
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STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
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S-8333 Series
Electrical Characteristics
Table 4 Electrical Characteristics
(Unless otherwise specified: VIN = 3.3 V, Ta = 25°C)
Parameter
Symbol
Operating input voltage VIN
FB voltage
VFB
Current consumption
ISS1
IEXTH
IEXTL
FB voltage temperature ∆VFB
coefficient
∆Ta
FB pin input current
IFB
EXT pin output current
Oscillation frequency*1
fosc
Oscillation frequency
∆fosc
temperature coefficient ∆Ta
Max. duty*2
MaxDuty
Soft-start time
tSS
Short-circuit protection
tPRO
*3
delay time
UVLO detection voltage VUVLO
UVLO hysteresis width VUVLOHYS
CC pin output current
ICCH
ICCL
VRTLT1
Timer latch reset voltage
VRTLT2
Conditions
Min.
Typ.
Max.
Unit
Test
Circuit
1.8
0.985
1.000
6.0
1.015
V
V
2
2
fosc = 700 kHz
VFB = 0.95 V
VEXT = VIN − 0.4 V
VEXT = 0.4 V
450
700
µA
1
100
−100
160
−60
mA
mA
1
1
Ta = −40 to +85°C
±100
ppm/°C
2
−0.1
+0.1
µA
1
fosc
× 0.9
fosc
fosc
× 1.1
kHz
1
1000
ppm/°C
1
%
1
When fosc = 1133 kHz is set
(ROSC = 120 kΩ)
When fosc = 700 kHz is set
(ROSC = 200 kΩ)
When fosc = 286 kHz is set
(ROSC = 510 kΩ)
VFB = 0.9 V
Waveform on EXT pin is measured.
Ta = −40 to +85°C
fosc = 700 kHz
fosc = 1133 kHz (ROSC = 120 kΩ)
MaxDuty = 88.5% (RDuty = 62 kΩ)
MaxDuty = 73% (RDuty = 180 kΩ)
MaxDuty = 47% (RDuty = 390 kΩ)
fosc = 700 kHz (ROSC = 200 kΩ)
MaxDuty = 88.5% (RDuty = 100 kΩ)
tSS = 10 ms, 15 ms, 20 ms
Selected in three steps
tPRO = 50 ms
(CSP = 0.1 µF)
VUVLO = 1.5 V to 2.3 V
Selected in 0.1 V steps
VUVLOHYS = 0.1 V to 0.3 V
Selected in 0.1 V steps
VFB = 2 V
VFB = 0 V
Within short-circuit protection delay
time
After short-circuit protection circuit
operated
MaxDuty
MaxDuty
MaxDuty
+5
−5
tSS
× 0.75
tSS
tSS
× 1.5
ms
1
37.5
50
75
ms
1
V
1
V
1
µA
µA
1
1
VUVLO
VUVLO
VUVLO
× 0.95
× 1.05
VUVLOHYS
VUVLOHYS
VUVLOHYS
× 0.6
× 1.4
−75
−50
−37.5
37.5
50
75
0.7
1.0
1.3
V
1
VUVLO
× 0.95
VUVLO
VUVLO
× 1.05
V
1
*1. The recommended range of the resistance (Rosc) for oscillation frequency is Rosc = 120 kΩ to 510 kΩ (fOSC = 286 kHz to 1.133 MHz).
This range of oscillation frequency is the typical value when an ideal resistor is connected externally. In actual use, it is necessary to
take account the dispersion of an IC (±10%) into this value.
*2. Set max. duty; Between 47 and 88.5 % (RDuty/ROSC = 0.5 to 3.2); the oscillation frequency is 500 kHz or more
Between 47 and 80 % (RDuty/ROSC = 1.0 to 3.2); the oscillation frequency is less than 500 kHz
This range of max. duty is the typical value when an ideal resistor is connected externally. In actual use, it is necessary to take
account the dispersion of an IC (±5%) into this value.
*3. The short-circuit protection time can be set by the external capacitor. Although the maximum set value by the external capacitor is
unlimited under the ideal condition, set CSP = approx. 0.47 µF as a target maximum value due to discharge time of the capacitor.
6
Seiko Instruments Inc.
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
External Parts When Measuring Electrical Characteristics
Table 5 External Parts
Element Name
Inductor
Diode
Output capacitor
Transistor
Oscillation frequency setting resistor
Maximum duty ratio setting resistor
Short-circuit protection delay time
setting capacitor
Output voltage setting resistor 1
Output voltage setting resistor 2
FB pin capacitor
Phase compensation resistor
Phase compensation capacitor
Symbol
L
SD
CL
M1
ROSC
RDuty
Manufacturer
TDK Corporation
Rohm Co., Ltd.
Sanyo Electric Co., Ltd.
CSP
RFB1
RFB2
CFB
RZ
CZ
Seiko Instruments Inc.
Part Number
LDR655312T 10 µH
RB491D
Ceramic 10 µF
MCH3406
200 kΩ (when fOSC = 700 kHz)
300 kΩ (when MaxDuty = 73%)
0.1 µF (when tPRO = 50 ms)
8.2 kΩ (when VOUT = 9.2 V)
1.0 kΩ (when VOUT = 9.2 V)
180 pF
200 kΩ
0.01 µF
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STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
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S-8333 Series
Measurement Circuits
1.
RZ
A
CZ
CSP
CC
RDuty
FB
ROSC
CSP
VSS
VIN
EXT
ROSC RDuty
CIN
Oscilloscope
Figure 5
2.
RFB1
RDuty
FB
ROSC
CFB
RZ
CZ
CC
SD
RFB2
CL
L
M1 CIN
CSP
VSS
VIN
EXT
CSP
V
Figure 6
8
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ROSC RDuty
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S-8333 Series
Operation
1. Switching control method
1. 1 PWM control
The S-8333 Series is a DC-DC converter using a pulse width modulation method (PWM).
The pulse width of the S-8333 Series varies from 0% to the maximum duty set by RDuty depending on the load
current, but its switching frequency does not change. Consequently, the ripple voltage generated from switching
can be removed easily via a filter.
2. Soft-start function
For this IC, the built-in soft-start circuit controls the rush current and overshoot of the output voltage when
powering on. Reference voltage adjustment and maximum duty control methods are adopted as the soft-start
methods. The following describes the soft-start function at power application.
In the circuit where the input voltage is not directly output at shutdown by inserting a switch (SW) between the
diode (SD) and VOUT output, the VOUT voltage when the VIN voltage is applied with the SW OFF stays 0 V.
Therefore, the voltage of the FB pin stays 0 V and the EXT output is in the step up status between the “H” and “L”
levels due to the maximum duty. The maximum duty at this time is approximately 7% and the rush current at
power application is controlled. The maximum duty soft start is accomplished by gradually increasing the duty
width up to the maximum duty set by the external resistor RDuty (refer to Figure 8).
The reference voltage of the error amplifier input also gradually increases from 0 V at the same time as the
maximum duty soft start. The increasing of the output voltage is controlled by turning the SW ON. The soft-start
function is realized by controlling the voltage of the FB pin so that it is the same potential as the reference voltage
that is slowly raised. A Rail-to-Rail amplifier is adopted as the error amplifier, which means that the voltage is
loop controlled so that it can be the same as the reference voltage.
Once the reference voltage rises, the voltage cannot be reset (the reference voltage is 0 V) unless making the
power supply voltage lower than the UVLO detection voltage. Conversely, when the power supply voltage rises
up to the reset voltage after it is lowered to the UVLO detection voltage or lower, the output voltage is stepped up
by the soft-start function.
SD
SW
VOUT
L
PWM
Comparator
VIN
M1
−
EXT
CC
RFB1
0.5 V
0V
+
FB
Error amplifier
+
Error amplifier
− reference voltage
RZ
CL
RFB2
Vref
CZ
Figure 7
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S-8333 Series
(VIN = 0 V→3.3 V, VOUT = 9.2 V, RFB1 = 8.2 kΩ, RFB2 = 1.0 kΩ)
3.3 V
Input voltage
(VIN)
0V
tSS
Output voltage
(VOUT)
9.2 V
VOUT×0.95
SW : ON
0V
1.0 V
Error amplifier
reference voltage
0V
Reference voltage soft-start period
1.0 V
FB pin voltage
(VFB)
0V
3.3 V
EXT pin voltage
(VEXT)
0V
Maximum duty
soft-start period
t (ms)
Figure 8
10
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3. Timer latch short-circuit protection function
This IC has a timer latch short-circuit protection circuit that stops the switching operation when the output voltage
drops for a specific time due to output short-circuiting. A capacitor (CSP) that is used to set the delay time of this
short-circuit protection circuit can be connected to the CSP pin.
This IC operates at the maximum duty ratio if the output voltage drops due to output short-circuiting. At the
maximum duty ratio, constant-current charging of CSP starts. If this status lasts for a short-circuit protection
delay time and the CSP pin voltage rises above the reference voltage, the latch mode is set. Note that the latch
mode is different from the shutdown status in that the switching operation is stopped but the internal circuitry
operates normally.
To reset the latch operation to protect the IC from short-circuiting, lower VIN than the UVLO detection voltage.
The latch mode within the short-circuit protection delay time is reset by decreasing VIN to 1.0 V (Typ.) or lower.
Note that the mode is not reset even if the VIN is lowered to the UVLO detection voltage (refer to Figure 9).
Input voltage
(VIN)
UVLO release
UVLO detection
1.0 V
Output load
CSP pin voltage
(VCSP)
Short-circuit status
Reference
voltage
50 ms (CSP = 0.1 µF)
Latch mode
Normal
status
Short-circuit
protection time
Latch
period
Short-circuit
protection time
Reset period
Short-circuit
protection time
Reset period
Figure 9
4. UVLO function
This IC includes a UVLO (under-voltage lockout) circuit to prevent the IC from malfunctioning due to a transient
status when power is applied or a momentary drop of the power supply voltage. When UVLO is in the detection
state, switching is stopped and the external FET is held in the off status. Once UVLO enters the detection state,
the soft-start function is reset.
Note that the other internal circuits operate normally and that the status is different from the power-off status.
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5. Error amplifier
The error amplifier outputs the PWM control signal so that the voltage of the FB pin is held at a specific value (1
V). By connecting a resistor (RZ) and capacitor (CZ) to the output pin (CC pin) of the error amplifier in series, an
optional loop gain can be set, enabling stabilized phase compensation.
6. Operation
The following are basic equations [(1) through (7)] of the step-up switching regulator (refer to Figure 10).
L
CONT
VIN
D
VOUT
EXT
M1
FB
CL
VSS
Figure 10 Step-up Switching Regulator Circuit for Basic Equations
Voltage at the CONT pin at the moment M1 is turned ON (current IL flowing through L is zero), VA:
*1
VA = VS ................................................................................................................................................. (1)
*1.
VS: Non-saturated voltage of M1
Change in IL over time:
V − VS
dl L
V
............................................................................................................................. (2)
= L = IN
dt
L
L
Integration of the above equation:
V − VS
IL = IN
t .................................................................................................................................... (3)
L
IL flows while M1 is ON (ton). This time is determined by the oscillation frequency of OSC.
Peak current (IPK) after tON:
V − VS
IPK = IN
t ON .............................................................................................................................. (4)
L
The energy stored in L is represented by
1
2
L (IPK ) .
2
When M1 is turned OFF (tOFF), the energy stored in L is released via a diode, generating a reverse voltage (VL).
VL :
(
VL = VOUT + VD
*2.
*2
)− V
IN
......................................................................................................................... (5)
VD: Diode forward voltage
The voltage on the CONT pin rises only by VOUT + VD.
12
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Change in current (IL) flowing through the diode into VOUT during tOFF:
+ VD − VIN
V
dI L
V
................................................................................................................. (6)
= L = OUT
dt
L
L
Integration of the above equation is as follows:
+ VD − VIN
V
IL = IPK − OUT
t ............................................................................................................... (7)
L
During tON, energy is stored in L and is not transmitted to VOUT. When receiving output current (IOUT) from VOUT,
the energy of the capacitor (CL) is used. As a result, the pin voltage of CL is reduced, and goes to the lowest level
after M1 is turned ON (tON). When M1 is turned OFF, the energy stored in L is transmitted via the diode to CL, and
the pin voltage of CL rises drastically. Because VOUT is a time function indicating the maximum value (ripple
voltage: Vp-p) when the current flowing through the diode into VOUT and the load current IOUT match.
Next, this ripple voltage is determined as follows.
IOUT vs t1 (time) from after tON, when VOUT reaches the maximum level:
+ VD − VIN
V
IOUT = IPK − OUT
L
t 1 .......................................................................................................... (8)
L
......................................................................................................... (9)
∴ t 1 = (IPK − IOUT )
+
−
V
V
V
D
IN
OUT
When tOFF, IL = 0 (when the energy of the inductor is completely transmitted):
Based on equation (7),
L
V
OUT + V D − V IN
t
= OFF ............................................................................................................ (10)
I PK
When substituting equation (10) for equation (9):
I
t 1 = t OFF − OUT
IPK
t OFF .................................................................................................................... (11)
Electrical charge ∆Q1 which is charged in CL during t1:
∆Q1 =
t1
∫0
t1
∫0
IL dt = IPK
dt −
V OUT + V D − V IN
L
t1
∫0
tdt = IPK t 1 −
V OUT + V D − V IN 1 2
t 1 ................. (12)
L
2
When substituting equation (12) for equation (9):
∆ Q 1 = IPK −
=
IPK + I OUT
t 1 ................................................................................... (13)
2
I PK + I OUT
2
t 1 ................................................................................................... (14)
1
(IPK − I OUT
2
) t1
A rise voltage (Vp-p) due to ∆Q1:
VP −P =
∆Q 1
1
=
CL
CL
When taking into consideration IOUT consumed during t1 and ESR*1 (RESR) of CL:
VP −P =
*1.
∆Q1
1
=
CL
CL
IPK + I OUT
2
+ I OUT
I
t 1 + PK
2
I
t
R ESR − OUT 1 .............................................. (15)
CL
Equivalent Series Resistance
When substituting equation (11) for equation (15):
VP −P =
(I PK − I OUT ) 2 t OFF
+ I OUT
I
+ PK
2 IPK
CL
2
R ESR ........................................................................... (16)
Therefore to reduce the ripple voltage, it is important that the capacitor connected to the output pin has a large
capacity and a small ESR.
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External Parts Selection
1. Inductor
The inductance has a strong influence on the maximum output current (IOUT) and efficiency (η).
The peak current (IPK) increases by decreasing L and the stability of the circuit improves and IOUT increases. If L
is decreased further, the efficiency falls, and IOUT decreases if the current drive capability of the external
transistor is insufficient.
The loss of IPK by the switching transistor decreases by increasing L and the efficiency becomes maximum at a
certain L value. Further increasing L decrease the efficiency due to the loss of the DC resistance of the inductor.
IOUT also decreases.
If the oscillation frequency is higher, a smaller L value can be chosen, making the inductor smaller. In the S-8333
Series, the oscillation frequency can be varied within the range of 286 kHz to 1.133 MHz by the external resistor,
so select an L value best suited to the frequency. The recommended value is between 2.2 µH and 22 µH.
When selecting an inductor, note the allowable current of the inductor. If a current exceeding this allowable
current flows through the inductor, magnetic saturation occurs, substantially lowering the efficiency and
increasing the current, which results in damage to the IC.
Therefore, select an inductor so that IPK does not exceed the allowable current. IPK is expressed by the following
equations in the discontinuous mode and continuous mode.
I PK =
I PK =
2 I OUT (V
OUT
fosc
+ V D − V IN )
L
( discontinuous mode ) .................................................................. (17)
(V OUT + V D − V IN ) V IN
V OUT + V D
I OUT +
V IN
2 (V OUT + V D ) fosc L
(continuous mode) ........................................................ (18)
fOSC = Oscillation frequency, VD ≅ 0.4 V.
2. Diode
Use an external diode that meets the following requirements.
• Low forward voltage
• High switching speed
• Reverse breakdown voltage: VOUT + [Spike voltage] or more
• Rated current: IPK or more
3. Capacitors (CIN, CL)
The capacitor on the input side (CIN) can lower the supply impedance and level the input current for better
efficiency. Select CIN according to the impedance of the power supply to be used.
The capacitor on the output side (CL) is used to smooth the output voltage. Select an appropriate capacitance
value based on the I/O conditions and load conditions. A capacitance of 10 µF or more is recommended.
By adjusting the phase compensation of the feedback loop using the external resistor (RZ) and capacitor (CZ), a
ceramic capacitor can be used as the capacitor on the output side. If a capacitor whose equivalent series
resistance is between 30 mΩ and 500 mΩ is used as the output capacitor, the adjustable range of the phase
compensation is wider; however, note that other characteristics may be affected by ripple voltage or other
conditions at this time. The optimal capacitor differs depending on the L value, capacitance value, wiring, and
application (output load), so select the capacitor after performing sufficient evaluation under the actual usage
conditions.
14
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S-8333 Series
4. External transistor
A bipolar (NPN) or enhancement (N-channel) MOS FET transistor can be used as the external capacitor.
4. 1 Bipolar (NPN) type
The driving capability when the output current is increased by using a bipolar transistor is determined by hFE
and Rb of the bipolar transistor. Figure 11 shows a peripheral circuit.
VIN
Cb
2200 pF
Pch
IPK
Rb
EXT
1 kΩ
Nch
Figure 11 External Transistor Periphery
1 kΩ is recommended for Rb. Actually, calculate the necessary base current (Ib) from hFE of the bipolar
transistor as follows and select an Rb value lower than this.
Ib =
Rb =
IPK
hFE
VIN − 0.7
Ib
−
0.4
IEXTH
A small Rb increases the output current, but the efficiency decreases. Actually, a pulsating current flows and
a voltage drop occurs due to the wiring capacitance. Determine the optimum value by experiment.
A speed-up capacitor (Cb) connected in parallel with Rb resistance as shown in Figure 11 decreases the
switching loss and improves the efficiency.
Select Cb by observing the following equation.
1
Cb ≤
2 π R b f OSC 0.7
However, in practice, the optimum Cb value also varies depending on the characteristics of the bipolar
transistor employed. Therefore, determine the optimum value of Cb by experiment.
4. 2 Enhancement MOS FET type
Use an Nch power MOS FET. For high efficiency, using a MOS FET with a low ON resistance (RON) and
small input capacitance (CISS) is ideal, however, ON resistance and input capacitance generally share a
trade-off relationship. The ON resistance is efficient in a range in which the output current is relatively great
during low-frequency switching, and the input capacitance is efficient in a range in which the output current
is middling during high-frequency switching.
Select a MOS FET whose ON resistance and input
capacitance are optimal depending on the usage conditions.
The input voltage (VIN) is supplied for the gate voltage of the MOS FET, so select a MOS FET with a gate
withstanding voltage that is equal to the maximum usage value of the input voltage or higher and a drain
withstanding voltage that is equal to the amount of the output voltage (VOUT) and diode voltage (VD) or
higher.
If a MOS FET with a threshold that is near the UVLO detection voltage is used, a large current may flow,
stopping the output voltage from rising and possibly generating heat in the worst case. Select a MOS FET
with a threshold that is sufficiently lower than the UVLO detection voltage value.
Seiko Instruments Inc.
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STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
5. Oscillation frequency and maximum duty ratio setting resistors (ROSC, RDuty)
With the S-8333 Series, the oscillation frequency can be set in a range of 286 kHz to 1.133 MHz using external
resistance. Connect a resistor across the ROSC and VSS pins. Select the resistor by using the following
equation and referring to Figure 12. However, the following equation and figure assume that the resistance
value is the desired value and show the theoretical values when the IC is in the typical conditions. Note that
fluctuations of resistance and IC are not considered.
140 × 103
fOSC [kHz]
1400
1200
fOSC [kHz]
ROSC [kΩ] ≅
1000
800
600
400
200
0
0
600
400
200
ROSC [kΩ]
Figure 12 ROSC vs. fOSC
With the S-8333 Series, the maximum duty ratio can be set in a range of 47% to 88.5% (between 47 to 80%, if the
oscillation frequency is less than 500 kHz) by an external resistor. Connect the resistor across the RDuty and
VSS pins. Select the resistance by using the following equation and referring to Figure 13. The maximum duty
ratio fluctuates according to the oscillation frequency. If the value of ROSC is changed, therefore, be sure to
change the value of RDuty so that it is always in proportion to RDuty / ROSC. However, the following equation
and figure assume that the resistance value is the desired value and show the theoretical values when the IC is
in the typical conditions. Note that fluctuations of resistance and IC are not considered.
Caution Set max. duty 80% or less if the oscillation frequency is less than 500 kHz.
RDuty
(95.5 − MaxDuty)
100
15.0
90
MaxDuty [%]
ROSC
≅
80
70
60
50
40
0
1
2
3
RDuty / ROSC
Figure 13 RDuty / ROSC vs. MaxDuty
Connect resistors ROSC and RDuty as close to the IC as possible.
16
Seiko Instruments Inc.
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6. Short-circuit protection delay time setting capacitor (CSP)
With the S-8333 Series, the short-circuit protection delay time can be set to any value by an external capacitor.
Connect the capacitor across the CSP and VSS pins. Select the capacitance by using the following equation and
referring to Figure 14. However, the following equation and figure assume that the capacitor value is the desired
value and show the theoretical values when the IC is in the typical conditions. Note that fluctuations of capacitor
and IC are not considered.
tPRO [ms] × 2 × 10−3
120
1.0
100
tPRO [ms]
CSP [µF] ≅
80
60
40
20
0
0
0.05
0.10
0.15
0.20
0.25
CSP [µF]
Figure 14 CSP vs. tPRO
7. Output voltage setting resistors (RFB1, RBF2)
With the S-8333 Series, the output voltage can be set to any value by external divider resistors.
Connect the divider resistors across the VOUT and VSS pins. Because VFB = 1 V, the output voltage can be
calculated by this equation.
VOUT =
(RFB1 + RFB2)
RFB2
Connect divider resistors RFB1 and RFB2 as close to the IC to minimize effects from of noise. If noise does have
an effect, adjust the values of RFB1 and RFB2 so that RFB1 + RFB2 < 100 kΩ.
CFB connected in parallel with RFB1 is a capacitor for phase compensation. Select the optimum value of this
capacitor at which the stable operation can be ensured from the values of the inductor and output capacitor.
8. Phase compensation setting resistor and capacitor (RZ, CZ)
The S-8333 Series needs appropriate compensation for the voltage feedback loop to prevent excessive output
ripple and unstable operation from deteriorating the efficiency. This compensation is implemented by connecting
RZ and CZ in series across the CC and VSS pins. RZ sets the high-frequency gain for a high-speed transient
response. CZ sets the pole and zero of the error amplifier and keeps the loop stable. Adjust RZ and CZ, taking
into consideration conditions such as the inductor, output capacitor, and load current, so that the optimum
transient characteristics can be obtained.
Seiko Instruments Inc.
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S-8333 Series
Standard Circuit
SD
L
VOUT
RDuty
VIN
UVLO
M1
CIN
ROSC
+
PWM −
comparator
EXT
+
Timer latch
short-circuit
protection circuit
0.1 µF
VSS
CSP
CFB RFB1
Oscillator
Maximum duty
soft-start circuit
Error amplifier
−
Reference voltage
(1.0 V)
soft-start circuit
CL
ROSC RDuty
FB
RFB2
CC
RZ
CZ
Ground point
Figure 15 Standard Circuit
Caution
18
The above connection diagram and constant will not guarantee successful operation.
Perform thorough evaluation using the actual application to set the constant.
Seiko Instruments Inc.
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Precaution
•
Mount external capacitors, diodes, and inductor as close as possible to the IC.
•
Characteristics ripple voltage and spike noise occur in IC containing switching regulators. Moreover rush current
flows at the time of a power supply injection. Because these largely depend on the inductor, the capacitor and
impedance of power supply used, fully check them using an actually mounted model.
•
Make sure the dissipation of the switching transistor (especially at a high temperature) does not exceed the
allowable power dissipation of the package.
•
The performance of a switching regulator varies depending on the design of the PCB patterns, peripheral circuits,
and external parts. Thoroughly test all settings with your device.
•
The capacitor, diode, inductor and others used as external parts do not assure the operation at high temperature.
Evaluate fully using the actual application when designing.
•
This IC builds in soft start function, starts reference voltage gradually, and it is controlled so that FB pin voltage and
reference voltage become this potential. Therefore, keep in mind that it will be in a maximum duty state according
to the factor of IC exterior if FB pin voltage is held less than reference voltage.
•
Although the IC contains a static electricity protection circuit, static electricity or voltage that exceeds the limit of the
protection circuit should not be applied.
•
Seiko Instruments Inc. assumes no responsibility for the way in which this IC is used on products created using this
IC or for the specifications of that product, nor does Seiko Instruments Inc. assume any responsibility for any
infringement of patents or copyrights by products that include this IC either in Japan or in other countries.
Seiko Instruments Inc.
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Characteristics (Typical Data)
1. Example of Major Temperature Characteristics (Ta = −40 to 85°C)
ISS1 [µA]
ISS1 vs. Ta (VIN = 3.3 V)
800
fOSC = 1133 kHz (ROSC = 120 kΩ)
700
600
fOSC = 700 kHz (ROSC = 200 kΩ)
500
400
300
fOSC = 286 kHz (ROSC = 510 kΩ)
200
100
0
−40 −20
0
20 40 60 80 100
Ta [°C]
100
MaxDuty [%]
100
fOSC vs. Ta (VIN = 3.3 V)
1400
fOSC = 1133 kHz (ROSC = 120 kΩ)
1200
1000
fOSC = 700 kHz (ROSC = 200 kΩ)
800
600
fOSC = 286 kHz (ROSC = 510 kΩ)
400
200
0
−40 −20
0
20 40 60 80 100
Ta [°C]
60
80
100
tSS vs. Ta (VIN = 3.3 V)
25.0
tSS = 20 ms
20.0
tSS [ms]
20 40
Ta [°C]
MaxDuty vs. Ta (VIN = 3.3 V)
100
90
MaxDuty = 88.5% (ROSC = 200 kΩ, RDuty = 100 kΩ)
80
70
MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
60
50
40
MaxDuty = 47% (ROSC = 200 kΩ, RDuty = 640 kΩ)
30
20
10
0
−40 −20
0
20 40 60 80 100
Ta [°C]
20
80
fOSC [kHz]
80
IFB [µA]
IFB vs. Ta (VIN = 3.3 V)
0.10
0.08
0.06
0.04
0.02
0
−0.02
−0.04
−0.06
−0.08
−0.10
−40 −20
0
IEXTL vs. Ta (VIN = 3.3 V)
200
180
160
140
120
100
80
60
fOSC = 700 kHz, MaxDuty = 73%
40
(ROSC = 200 kΩ, RDuty = 300 kΩ)
20
0
−40 −20
0
20 40 60
Ta [°C]
IEXTL [mA]
IEXTH [mA]
IEXTH vs. Ta (VIN = 3.3 V)
−200
−180
−160
−140
−120
−100
−80
−60
fOSC = 700 kHz, MaxDuty = 73%
−40
(ROSC = 200 kΩ, RDuty = 300 kΩ)
−20
0
−40 −20
0
20 40 60
Ta [°C]
15.0
tSS = 10 ms
10.0
5.0
0
−40 −20
Seiko Instruments Inc.
0
20 40
Ta [°C]
60
80
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VUVLO vs. Ta
2.5
VUVLOHYS vs. Ta
0.35
0.30
0.25
0.20
0.15
0.10
0.05
0
−40 −20
ICCH vs. Ta (VIN = 3.3 V)
−100
−90
−80
−70
−60
−50
−40
−30
−20
−10
0
−40 −20
0
20 40
Ta [°C]
VUVLO = 2.3 V
1.5
VUVLO = 1.5 V
1.0
0.5
0
−40 −20
0
20 40
Ta [°C]
60
80
100
60
80
100
60
80
100
ICCH [µA]
VUVLOHYS [V]
VUVLOHYS = 0.3 V
2.0
VUVLO [V]
tPRO [ms]
tPRO vs. Ta (VIN = 3.3 V)
70.0
tPRO = 50 ms (CSP = 0.1 µF)
60.0
50.0
40.0
30.0
20.0
10.0
0
−40 −20
0
20 40 60 80 100
Ta [°C]
VUVLOHYS = 0.1 V
20 40
Ta [°C]
80
100
VRTLT1 vs. Ta (VIN = 3.3 V)
1.2
1.0
ICCL [µA]
ICCL vs. Ta (VIN = 3.3 V)
100
90
80
70
60
50
40
30
20
10
0
−40 −20
0
20 40
Ta [°C]
60
VRTLT1 [V]
0
0.8
0.6
0.4
0.2
60
80
100
0
−40 −20
Seiko Instruments Inc.
0
20 40
Ta [°C]
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2. Example of Major Power Supply Dependence Characteristics (Ta = 25°C)
ISS1 [µA]
ISS vs. VIN
1400
fOSC = 1133 kHz
1200 (ROSC = 120 kΩ)
1000
fOSC = 700 kHz
800 (ROSC = 200 kΩ)
600
400
fOSC = 286 kHz
200
(ROSC = 510 kΩ)
0
7
1
0
2
3
4
5
6
VIN [V]
6
7
MaxDuty [%]
fOSC [kHz]
2
3
4
VIN [V]
5
6
7
7
600
400
200
0
6
7
fOSC = 286 kHz (ROSC = 510 kΩ)
0
1
2
3
4
VIN [V]
5
tSS vs. VIN
25.0
20.0
MaxDuty = 88.5% (ROSC = 200 kΩ, RDuty = 100 kΩ)
tSS [ms]
1
MaxDuty vs. VIN
100
90
80
70
60
50
40
30
20
10
0
1
0
22
6
fOSC vs. VIN
1400
1200 fOSC = 1133 kHz (ROSC = 120 kΩ)
1000
800 fOSC = 700 kHz (ROSC = 200 kΩ)
IFB [µA]
IFB vs. VIN
0.10
0.08
0.06
0.04
0.02
0
−0.02
−0.04
−0.06
−0.08
−0.10
0
IEXTL vs. VIN
200
180
160
140
120
100
80
60 fOSC = 700 kHz, MaxDuty = 73%
40 (ROSC = 200 kΩ, RDuty = 300 kΩ)
20
0
1
0
2
3
4
5
VIN [V]
IEXTL [mA]
IEXTH [mA]
IEXTH vs. VIN
−200
−180
−160
−140
−120
−100
−80
−60
fOSC = 700 kHz, MaxDuty = 73%
−40
(ROSC = 200 kΩ, RDuty = 300 kΩ)
−20
0
1
0
2
3
4
5
VIN [V]
MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
MaxDuty = 47% (ROSC = 200 kΩ, RDuty = 640 kΩ)
tSS = 20 ms
15.0
10.0
tSS = 10 ms
5.0
0
2
3
4
VIN [V]
5
6
7
0
Seiko Instruments Inc.
1
2
3
4
VIN [V]
5
6
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tPRO vs. VIN
70.0
60.0
50.0
40.0
30.0
20.0
10.0
0
0
1
2
3
4
VIN [V]
5
6
7
ICCL vs. VIN
100
90
80
70
60
50
40
30
20
10
0
0
1
2
3
4
VIN [V]
5
6
7
ICCH [µA]
tPRO [ms]
tPRO=50 ms (CSP = 0.1 µF)
ICCH vs. VIN
−100
−90
−80
−70
−60
−50
−40
−30
−20
−10
0
0
2
3
4
VIN [V]
5
6
7
ICCL [µA]
1
Seiko Instruments Inc.
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3. Example of External Parts Dependence Characteristics
fOSC [kHz]
fOSC vs. ROSC (VIN = 3.3 V)
1600
1400
Ta = −40°C
1200
Ta = 25°C
1000
Ta = 85°C
800
600
400
200
0
100 200 300 400 500
0
ROSC [kΩ]
600
MaxDuty [%]
MaxDuty vs. RDuty / ROSC (ROSC = 200 kΩ, VIN = 3.3 V)
100
90
Ta = −40°C
80
Ta = 25°C
70
Ta = 85°C
60
50
40
30
20
10
0
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5
RDuty / ROSC
tPRO [ms]
tPRO vs. CSP (VIN = 3.3 V)
350
300
250
200
150
100
50
0
0.1
0
0.2
0.3
CSP [µF]
24
Ta = −40°C
Ta = 25°C
Ta = 85°C
0.4
0.5
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4. Examples of Transient Response Characteristics
4.1 Powering ON (VOUT = 9.2 V, VIN = 0 V → 3.3 V, Ta = 25°C)
Remark The switch (SW) is inserted between the diode (SD) and VOUT output.
Controlled externally to turn SW on a few ms later after the VIN voltage is applied.
(2) fOSC = 1133 kHz, IOUT = 100 mA, tSS = 10 ms
8
4
0
2
0
5
10
time [ms]
15
4
2
0
−5
20
(3) fOSC = 700 kHz, IOUT = 0 mA, tSS = 10 ms
0
0
5
10
time [ms]
15
20
(4) fOSC = 700 kHz, IOUT = 100 mA, tSS = 10 ms
12
8
4
0
2
0
−5
0
5
10
time [ms]
15
8
4
VIN [V]
VIN [V]
4
VOUT [V]
12
4
(5) fOSC = 286 kHz, IOUT = 0 mA, tSS = 10 ms
0
2
0
−5
20
0
5
10
time [ms]
15
20
(6) fOSC = 286 kHz, IOUT = 100 mA, tSS = 10 ms
12
4
0
2
0
−5
0
5
10
time [ms]
15
20
8
4
VIN [V]
VIN [V]
4
VOUT [V]
12
8
VOUT [V]
0
4
4
VOUT [V]
−5
12
8
VIN [V]
VIN [V]
4
VOUT [V]
12
VOUT [V]
(1) fOSC = 1133 kHz, IOUT = 0 mA, tSS = 10 ms
0
2
0
−5
Seiko Instruments Inc.
0
5
10
time [ms]
15
20
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4.2 Load fluctuations (VOUT = 9.2 V, VIN = 3.3 V, Ta = 25°C, RZ = 200 kΩ, CZ = 0.01 µF)
(1) fOSC = 1133 kHz, IOUT = 0.1 mA→100 mA
IOUT
100 mA
(2) fOSC = 1133 kHz, IOUT = 100 mA→0.1 mA
10.0
0.1 mA
9.8
IOUT
100 mA
9.6
0.1 mA
10.0
9.8
9.6
9.4
9.2
VOUT
[0.2 V/div]
−20
9.0
−10
0
time [ms]
10
20
(3) fOSC = 700 kHz, IOUT = 0.1 mA→100 mA
IOUT
100 mA
8.8
9.4
9.2
VOUT
[0.2 V/div]
−20
9.0
−10
0
time [ms]
10
20
(4) fOSC = 700 kHz, IOUT = 100 mA→0.1 mA
10.0
0.1 mA
9.8
IOUT
100 mA
9.6
0.1 mA
10.0
9.8
9.6
9.4
9.2
VOUT
[0.2 V/div]
−20
9.0
−10
0
time [ms]
10
20
(5) fOSC = 286 kHz, IOUT = 0.1 mA→100 mA
IOUT
100 mA
8.8
9.4
9.2
VOUT
[0.2 V/div]
−20
9.0
−10
0
time [ms]
10
20
9.8
IOUT
100 mA
9.6
0.1 mA
10.0
9.8
9.6
9.4
9.2
VOUT
[0.2 V/div]
26
9.0
−10
0
time [ms]
10
8.8
(6) fOSC = 286 kHz, IOUT = 100 mA→0.1 mA
10.0
0.1 mA
−20
8.8
20
8.8
9.4
9.2
VOUT
[0.2 V/div]
−20
Seiko Instruments Inc.
9.0
−10
0
time [ms]
10
20
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4.3 Input voltage fluctuations (VOUT = 9.2 V, IOUT = 100 mA, RZ = 200 kΩ, CZ = 0.01 µF)
(1) fOSC = 1133 kHz, VIN = 2.8 V→3.8 V
4.0
VIN 3.5
[V] 3.0
2.5
−20
−10
0
time [ms]
10
(3) fOSC = 700 kHz, VIN = 2.8 V→3.8 V
4.0
VIN 3.5
[V] 3.0
2.5
−20
−10
0
time [ms]
10
(5) fOSC = 286 kHz, VIN = 2.8 V→3.8 V
4.0
VIN 3.5
[V] 3.0
2.5
−20
−10
0
time [ms]
10
9.40
9.30 VOUT
9.20 [V]
9.10
20
9.40
9.30 VOUT
9.20 [V]
9.10
20
9.40
9.30 VOUT
9.20 [V]
9.10
20
(2) fOSC = 1133 kHz, VIN = 3.8 V→2.8 V
4.0
VIN 3.5
[V] 3.0
2.5
−20
−10
0
time [ms]
10
(4) fOSC = 700 kHz, VIN = 3.8 V→2.8 V
4.0
VIN 3.5
[V] 3.0
2.5
−20
−10
0
time [ms]
10
(6) fOSC = 286 kHz, VIN = 3.8 V→2.8 V
4.0
VIN 3.5
[V] 3.0
2.5
−20
Seiko Instruments Inc.
−10
0
time [ms]
10
9.40
9.30 VOUT
9.20 [V]
9.10
20
9.40
9.30 VOUT
9.20 [V]
9.10
20
9.40
9.30 VOUT
9.20 [V]
9.10
20
27
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
Reference Data
1. Reference data for external parts
Table 6 Properties of External Parts
Element Name
Inductor
Diode
Output capacitor
(ceramic)
Transistor
Product Name
Manufacture
LDR655312T
TDK Corporation
RB491D
Rohm Co., Ltd.
MCH3406
Sanyo Electric Co., Ltd.
Characteristics
10 µH, DCR*1 = 307 mΩ, IMAX*2 = 0.7 A,
Height = 1.2 mm
VF*3 = 0.45 V, IF*4 = 1.0 A
16 V, 10 µF
VDSS*5 = 20 V, VGSS*6 = ±10 V, Ciss*7 = 280 pF,
RDS(ON)*8 = 82 mΩ max. (VGS*9 = 2.5 V, ID*10 = 1 A)
*1. DCR :
DC resistance
*2. IMAX :
Maximum allowable current
*3. VF :
Forward voltage
*4. IF :
Forward current
*5. VDSS :
Drain to source voltage (when short circuited between the gate and source)
*6. VGSS :
Gate to source voltage (when short circuited between the drain and source)
*7. Ciss :
Input capacitance
*8. RDS(ON) : Drain to source on resistance
*9. VGS :
Gate to source voltage
*10. ID :
Drain current
Caution The values shown in the characteristics column of Table 6 above are based on the materials
provided by each manufacturer. However, consider the characteristics of the original materials
when using the above products.
28
Seiko Instruments Inc.
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
2. Reference data (1)
The data of (a) output current (IOUT) vs. efficiency (η) characteristics and (b) output current (IOUT) vs. output voltage
(VOUT) characteristics is shown below.
2. 1 VOUT = 13.1 V (RFB1 = 7.5 kΩ, RFB2 = 620 Ω)
(1) fOSC = 1133 kHz, MaxDuty = 73% (ROSC = 120 kΩ, RDuty = 180 kΩ)
(b) IOUT vs. VOUT
13.20
VOUT [V]
13.15
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
1
10
IOUT [mA]
100
13.05
13.00
12.95
VIN = 5.0 V
0.1
13.10
12.90
0.01
1000
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
1000
(2) fOSC = 700 kHz, MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
(b) IOUT vs. VOUT
13.20
VOUT [V]
13.15
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
1
10
IOUT [mA]
100
13.05
13.00
12.95
VIN = 5.0 V
0.1
13.10
12.90
0.01
1000
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
1000
(3) fOSC = 286 kHz, MaxDuty = 73% (ROSC = 510 kΩ, RDuty = 750 kΩ)
(b) IOUT vs. VOUT
13.20
VOUT [V]
13.15
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
1000
13.10
13.05
13.00
12.95
12.90
0.01
Seiko Instruments Inc.
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
1000
29
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
2. 2 VOUT = 9.2 V (RFB1 = 8.2 kΩ, RFB2 = 1.0 kΩ)
(1) fOSC = 1133 kHz, MaxDuty = 73% (ROSC = 120 kΩ, RDuty = 180 kΩ)
(b) IOUT vs. VOUT
9.30
VOUT [V]
9.25
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
VIN = 3.3 V
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
9.20
9.15
9.10
VIN = 3.3 V
VIN = 5.0 V
9.05
9.00
0.01
1000
0.1
1
10
IOUT [mA]
100
1000
(2) fOSC = 700 kHz, MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
(b) IOUT vs. VOUT
9.30
VOUT [V]
9.25
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
VIN = 3.3 V
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
9.20
9.15
9.10
VIN = 3.3 V
VIN = 5.0 V
9.05
9.00
0.01
1000
0.1
1
10
IOUT [mA]
100
1000
(3) fOSC = 286 kHz, MaxDuty = 73% (ROSC = 510 kΩ, RDuty = 750 kΩ)
(b) IOUT vs. VOUT
9.30
VOUT [V]
9.25
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
30
VIN = 3.3 V
VIN = 5.0 V
0.1
1
10
IOUT [mA]
100
1000
9.20
9.15
9.10
VIN = 3.3 V
VIN = 5.0 V
9.05
9.00
0.01
Seiko Instruments Inc.
0.1
1
10
IOUT [mA]
100
1000
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
2. 3 VOUT = 6.1 V (RFB1 = 5.1 kΩ, RFB2 = 1.0 kΩ)
(1) fOSC = 1133 kHz, MaxDuty = 73% (ROSC = 120 kΩ, RDuty = 180 kΩ)
(b) IOUT vs. VOUT
6.20
VOUT [V]
6.15
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
VIN = 2.5 V
VIN = 3.3 V
0.1
1
10
IOUT [mA]
100
6.10
6.05
6.00
VIN = 2.5 V
VIN = 3.3 V
5.95
5.90
0.01
1000
0.1
1
10
IOUT [mA]
100
1000
(2) fOSC = 700 kHz, MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
(b) IOUT vs. VOUT
6.20
VOUT [V]
6.15
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
VIN = 2.5 V
VIN = 3.3 V
0.1
1
10
IOUT [mA]
100
6.10
6.05
6.00
VIN = 2.5 V
VIN = 3.3 V
5.95
5.90
0.01
1000
0.1
1
10
IOUT [mA]
100
1000
(3) fOSC = 286 kHz, MaxDuty = 73% (ROSC = 510 kΩ, RDuty = 750 kΩ)
(b) IOUT vs. VOUT
6.20
VOUT [V]
6.15
η [%]
(a) IOUT vs. η
100
90
80
70
60
50
40
30
20
10
0
0.01
VIN = 2.5 V
VIN = 3.3 V
0.1
1
10
IOUT [mA]
100
1000
6.10
6.05
6.00
VIN = 2.5 V
VIN = 3.3 V
5.95
5.90
0.01
Seiko Instruments Inc.
0.1
1
10
IOUT [mA]
100
1000
31
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
3. Reference data (2)
The data of output current (IOUT) vs. ripple voltage (Vr) characteristics is shown below.
3. 1 VOUT = 13.1 V (RFB1 = 7.5 kΩ, RFB2 = 620 Ω)
100
1000
100
1000
100
1000
100
1000
Vr [mV]
(3) fOSC = 286 kHz, MaxDuty = 73%
(ROSC = 510 kΩ, RDuty = 750 kΩ)
100
90
VIN = 5.0 V
80
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
(2) fOSC = 700 kHz, MaxDuty = 73%
(ROSC = 200 kΩ, RDuty = 300 kΩ)
100
90
VIN = 5.0 V
80
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
Vr [mV]
Vr [mV]
(1) fOSC = 1133 kHz, MaxDuty = 73 %
(ROSC = 120 kΩ, RDuty = 180 kΩ)
100
90
VIN = 5.0 V
80
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
3. 2 VOUT = 9.2 V (RFB1 = 8.2 kΩ, RFB2 = 1.0 kΩ)
100
1000
100
1000
Vr [mV]
(3) fOSC = 286 kHz, MaxDuty = 73%
(ROSC = 510 kΩ, RDuty = 750 kΩ)
100
VIN = 3.3 V
90
80
VIN = 5.0 V
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
(2) fOSC = 700 kHz, MaxDuty = 73%
(ROSC = 200 kΩ, RDuty = 300 kΩ)
100
90
VIN = 3.3 V
80
VIN = 5.0 V
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
Vr [mV]
Vr [mV]
(1) fOSC = 1133 kHz, MaxDuty = 73%
(ROSC = 120 kΩ, RDuty = 180 kΩ)
100
90
VIN = 3.3 V
80
VIN = 5.0 V
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
32
Seiko Instruments Inc.
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
3. 3 VOUT = 6.1 V (RFB1 = 5.1 kΩ, RFB2 = 1.0 kΩ)
100
1000
100
1000
100
1000
Vr [mV]
(3) fOSC = 286 kHz, MaxDuty = 73%
(ROSC = 510 kΩ, RDuty = 750 kΩ)
100
VIN = 2.5 V
90
80
VIN = 3.3 V
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
(2) fOSC = 700 kHz, MaxDuty = 73%
(ROSC = 200 kΩ, RDuty = 300 kΩ)
100
VIN = 2.5 V
90
80
VIN = 3.3 V
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
Vr [mV]
Vr [mV]
(1) fOSC = 1133 kHz, MaxDuty = 73%
(ROSC = 120 kΩ, RDuty = 180 kΩ)
100
90
VIN = 2.5 V
80
VIN = 3.3 V
70
60
50
40
30
20
10
0
0.1
0.01
1
10
IOUT [mA]
Seiko Instruments Inc.
33
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
Marking Specification
(1) SNT-8A
SNT-8A
Top view
(1) (2) (3) (4)
(9) (10) (11)
4
(5) (6) (7) (8)
1
(1)
(2) to (4)
(5), (6)
(7) to (11)
8
Blank
Product code (Refer to Product name vs. Product code)
Blank
Lot number
5
Product name vs. Product code
Product name
S-8333AAAA-I8T1G
S-8333AAAB-I8T1G
S-8333AAAC-I8T1G
S-8333AABA-I8T1G
S-8333AABB-I8T1G
S-8333AABC-I8T1G
S-8333AACA-I8T1G
S-8333AACB-I8T1G
S-8333AACC-I8T1G
S-8333AADA-I8T1G
S-8333AADB-I8T1G
S-8333AADC-I8T1G
S-8333AAEA-I8T1G
S-8333AAEB-I8T1G
S-8333AAEC-I8T1G
S-8333AAFA-I8T1G
S-8333AAFB-I8T1G
S-8333AAFC-I8T1G
S-8333AAGA-I8T1G
S-8333AAGB-I8T1G
S-8333AAGC-I8T1G
S-8333AAHA-I8T1G
S-8333AAHB-I8T1G
S-8333AAHC-I8T1G
S-8333AAIA-I8T1G
S-8333AAIB-I8T1G
S-8333AAIC-I8T1G
S-8333ABAA-I8T1G
S-8333ABAB-I8T1G
S-8333ABAC-I8T1G
S-8333ABBA-I8T1G
S-8333ABBB-I8T1G
S-8333ABBC-I8T1G
S-8333ABCA-I8T1G
S-8333ABCB-I8T1G
S-8333ABCC-I8T1G
S-8333ABDA-I8T1G
S-8333ABDB-I8T1G
S-8333ABDC-I8T1G
S-8333ABEA-I8T1G
S-8333ABEB-I8T1G
34
(2)
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
O
Product code
(3)
(4)
F
A
F
B
F
C
F
D
F
E
F
F
F
G
F
H
F
I
F
J
F
K
F
L
F
M
F
N
F
O
F
P
F
Q
F
R
F
S
F
T
F
U
F
V
F
W
F
X
F
Y
F
Z
F
3
G
A
G
B
G
C
G
D
G
E
G
F
G
G
G
H
G
I
G
J
G
K
G
L
G
M
G
N
Product name
S-8333ABEC-I8T1G
S-8333ABFA-I8T1G
S-8333ABFB-I8T1G
S-8333ABFC-I8T1G
S-8333ABGA-I8T1G
S-8333ABGB-I8T1G
S-8333ABGC-I8T1G
S-8333ABHA-I8T1G
S-8333ABHB-I8T1G
S-8333ABHC-I8T1G
S-8333ABIA-I8T1G
S-8333ABIB-I8T1G
S-8333ABIC-I8T1G
S-8333ACAA-I8T1G
S-8333ACAB-I8T1G
S-8333ACAC-I8T1G
S-8333ACBA-I8T1G
S-8333ACBB-I8T1G
S-8333ACBC-I8T1G
S-8333ACCA-I8T1G
S-8333ACCB-I8T1G
S-8333ACCC-I8T1G
S-8333ACDA-I8T1G
S-8333ACDB-I8T1G
S-8333ACDC-I8T1G
S-8333ACEA-I8T1G
S-8333ACEB-I8T1G
S-8333ACEC-I8T1G
S-8333ACFA-I8T1G
S-8333ACFB-I8T1G
S-8333ACFC-I8T1G
S-8333ACGA-I8T1G
S-8333ACGB-I8T1G
S-8333ACGC-I8T1G
S-8333ACHA-I8T1G
S-8333ACHB-I8T1G
S-8333ACHC-I8T1G
S-8333ACIA-I8T1G
S-8333ACIB-I8T1G
S-8333ACIC-I8T1G
Seiko Instruments Inc.
Product code
(2)
(3)
(4)
O
G
O
O
G
P
O
G
Q
O
G
R
O
G
S
O
G
T
O
G
U
O
G
V
O
G
W
O
G
X
O
G
Y
O
G
Z
O
G
3
O
H
A
O
H
B
O
H
C
O
H
D
O
H
E
O
H
F
O
H
G
O
H
H
O
H
I
O
H
J
O
H
K
O
H
L
O
H
M
O
H
N
O
H
O
O
H
P
O
H
Q
O
H
R
O
H
S
O
H
T
O
H
U
O
H
V
O
H
W
O
H
X
O
H
Y
O
H
Z
O
H
3
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.2.3_00
S-8333 Series
(2) 8-Pin TSSOP
8-Pin TSSOP
Top view
1
(1) to (4)
(5) to (8)
8 (9) to (14)
(1) (2) (3) (4)
Product name: 8333 (Fixed)
Function code (Refer to Product name vs. Function code)
Lot number
(5) (6) (7) (8)
4
(9) (10) (11) (12) (13) (14)
5
Product name vs. Function code
Product name
S-8333AAAA-T8T1G
S-8333AAAB-T8T1G
S-8333AAAC-T8T1G
S-8333AABA-T8T1G
S-8333AABB-T8T1G
S-8333AABC-T8T1G
S-8333AACA-T8T1G
S-8333AACB-T8T1G
S-8333AACC-T8T1G
S-8333AADA-T8T1G
S-8333AADB-T8T1G
S-8333AADC-T8T1G
S-8333AAEA-T8T1G
S-8333AAEB-T8T1G
S-8333AAEC-T8T1G
S-8333AAFA-T8T1G
S-8333AAFB-T8T1G
S-8333AAFC-T8T1G
S-8333AAGA-T8T1G
S-8333AAGB-T8T1G
S-8333AAGC-T8T1G
S-8333AAHA-T8T1G
S-8333AAHB-T8T1G
S-8333AAHC-T8T1G
S-8333AAIA-T8T1G
S-8333AAIB-T8T1G
S-8333AAIC-T8T1G
S-8333ABAA-T8T1G
S-8333ABAB-T8T1G
S-8333ABAC-T8T1G
S-8333ABBA-T8T1G
S-8333ABBB-T8T1G
S-8333ABBC-T8T1G
S-8333ABCA-T8T1G
S-8333ABCB-T8T1G
S-8333ABCC-T8T1G
S-8333ABDA-T8T1G
S-8333ABDB-T8T1G
S-8333ABDC-T8T1G
S-8333ABEA-T8T1G
S-8333ABEB-T8T1G
(5)
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
Function code
(6) (7) (8)
A
A
A
A
A
B
A
A
C
A
B
A
A
B
B
A
B
C
A
C
A
A
C
B
A
C
C
A
D
A
A
D
B
A
D
C
A
E
A
A
E
B
A
E
C
A
F
A
A
F
B
A
F
C
A
G
A
A
G
B
A
G
C
A
H
A
A
H
B
A
H
C
A
I
A
A
I
B
A
I
C
B
A
A
B
A
B
B
A
C
B
B
A
B
B
B
B
B
C
B
C
A
B
C
B
B
C
C
B
D
A
B
D
B
B
D
C
B
E
A
B
E
B
Product name
S-8333ABEC-T8T1G
S-8333ABFA-T8T1G
S-8333ABFB-T8T1G
S-8333ABFC-T8T1G
S-8333ABGA-T8T1G
S-8333ABGB-T8T1G
S-8333ABGC-T8T1G
S-8333ABHA-T8T1G
S-8333ABHB-T8T1G
S-8333ABHC-T8T1G
S-8333ABIA-T8T1G
S-8333ABIB-T8T1G
S-8333ABIC-T8T1G
S-8333ACAA-T8T1G
S-8333ACAB-T8T1G
S-8333ACAC-T8T1G
S-8333ACBA-T8T1G
S-8333ACBB-T8T1G
S-8333ACBC-T8T1G
S-8333ACCA-T8T1G
S-8333ACCB-T8T1G
S-8333ACCC-T8T1G
S-8333ACDA-T8T1G
S-8333ACDB-T8T1G
S-8333ACDC-T8T1G
S-8333ACEA-T8T1G
S-8333ACEB-T8T1G
S-8333ACEC-T8T1G
S-8333ACFA-T8T1G
S-8333ACFB-T8T1G
S-8333ACFC-T8T1G
S-8333ACGA-T8T1G
S-8333ACGB-T8T1G
S-8333ACGC-T8T1G
S-8333ACHA-T8T1G
S-8333ACHB-T8T1G
S-8333ACHC-T8T1G
S-8333ACIA-T8T1G
S-8333ACIB-T8T1G
S-8333ACIC-T8T1G
Seiko Instruments Inc.
(5)
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
Function code
(6)
(7)
B
E
B
F
B
F
B
F
B
G
B
G
B
G
B
H
B
H
B
H
B
I
B
I
B
I
C
A
C
A
C
A
C
B
C
B
C
B
C
C
C
C
C
C
C
D
C
D
C
D
C
E
C
E
C
E
C
F
C
F
C
F
C
G
C
G
C
G
C
H
C
H
C
H
C
I
C
I
C
I
(8)
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
35
1.97±0.03
8
7
6
5
3
4
+0.05
1
0.5
2
0.08 -0.02
0.48±0.02
0.2±0.05
No. PH008-A-P-SD-2.0
TITLE
SNT-8A-A-PKG Dimensions
PH008-A-P-SD-2.0
No.
SCALE
UNIT
mm
Seiko Instruments Inc.
+0.1
ø1.5 -0
5°
2.25±0.05
4.0±0.1
2.0±0.05
ø0.5±0.1
0.25±0.05
0.65±0.05
4.0±0.1
4 321
5 6 78
Feed direction
No. PH008-A-C-SD-1.0
TITLE
SNT-8A-A-Carrier Tape
PH008-A-C-SD-1.0
No.
SCALE
UNIT
mm
Seiko Instruments Inc.
12.5max.
9.0±0.3
Enlarged drawing in the central part
ø13±0.2
(60°)
(60°)
No. PH008-A-R-SD-1.0
TITLE
SNT-8A-A-Reel
No.
PH008-A-R-SD-1.0
SCALE
UNIT
QTY.
mm
Seiko Instruments Inc.
5,000
0.52
2.01
0.52
0.3
0.2
0.3
0.2
0.3
0.2
0.3
Caution Making the wire pattern under the package is possible. However, note that the package
may be upraised due to the thickness made by the silk screen printing and of a solder
resist on the pattern because this package does not have the standoff.
No. PH008-A-L-SD-3.0
TITLE
SNT-8A-A-Land Recommendation
PH008-A-L-SD-3.0
No.
SCALE
UNIT
mm
Seiko Instruments Inc.
+0.3
3.00 -0.2
8
5
1
4
0.17±0.05
0.2±0.1
0.65
No. FT008-A-P-SD-1.1
TITLE
TSSOP8-E-PKG Dimensions
FT008-A-P-SD-1.1
No.
SCALE
UNIT
mm
Seiko Instruments Inc.
4.0±0.1
2.0±0.05
ø1.55±0.05
0.3±0.05
+0.1
8.0±0.1
ø1.55 -0.05
(4.4)
+0.4
6.6 -0.2
1
8
4
5
Feed direction
No. FT008-E-C-SD-1.0
TITLE
TSSOP8-E-Carrier Tape
FT008-E-C-SD-1.0
No.
SCALE
UNIT
mm
Seiko Instruments Inc.
13.4±1.0
17.5±1.0
Enlarged drawing in the central part
ø21±0.8
2±0.5
ø13±0.5
No. FT008-E-R-SD-1.0
TSSOP8-E-Reel
TITLE
No.
FT008-E-R-SD-1.0
SCALE
QTY.
UNIT
mm
Seiko Instruments Inc.
3,000
•
•
•
•
•
•
The information described herein is subject to change without notice.
Seiko Instruments Inc. is not responsible for any problems caused by circuits or diagrams described herein
whose related industrial properties, patents, or other rights belong to third parties. The application circuit
examples explain typical applications of the products, and do not guarantee the success of any specific
mass-production design.
When the products described herein are regulated products subject to the Wassenaar Arrangement or other
agreements, they may not be exported without authorization from the appropriate governmental authority.
Use of the information described herein for other purposes and/or reproduction or copying without the
express permission of Seiko Instruments Inc. is strictly prohibited.
The products described herein cannot be used as part of any device or equipment affecting the human
body, such as exercise equipment, medical equipment, security systems, gas equipment, or any apparatus
installed in airplanes and other vehicles, without prior written permission of Seiko Instruments Inc.
Although Seiko Instruments Inc. exerts the greatest possible effort to ensure high quality and reliability, the
failure or malfunction of semiconductor products may occur. The user of these products should therefore
give thorough consideration to safety design, including redundancy, fire-prevention measures, and
malfunction prevention, to prevent any accidents, fires, or community damage that may ensue.
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