U211B

Features • • • • • • • • • • • Internal Frequency-to-voltage Converter Externally Controlled Integrated Amplifier Overload Limitation with “Fold Back” Characteristic Optimized Soft-start Function Tacho Monitoring for Shorted and Open Loop Automatic Retriggering Switchable Triggering Pulse Typically 155 mA Voltage and Current Synchronization Internal Supply-voltage Monitoring Temperature Reference Source Current Requirement ≤3 mA 1. Description The integrated circuit U211B is designed as a phase-control circuit in bipolar technology with an internal frequency-to-voltage converter. The device includes an internal control amplifier which means it can be used for speed-regulated motor applications. Amongst others, the device features integrated load limitation, tacho monitoring and soft-start functions, to realize sophisticated motor control systems. Figure 1-1. Block Diagram 17(16) 1(1) 5* Automatic retriggering Output pulse 4(4) Phase Control IC with Overload Limitation for Tacho Applications U211B Voltage/current detector Control amplifier 11(10) + 10(9) - 6(5) 7(6) Phasecontrol unit ϕ = f (V12) 3(3) Supply voltage limitation Reference voltage Voltage monitoring 2(2) -VS GND 14(13) Load limitation speed/time controlled 16(15) 15(14) Controlled current sink -VRef 12(11) Pin numbers in brackets refer to SO16 * Pins 5 and 18 connected internally Soft start Frequencyto-voltage converter 9(8) 8(7) Pulse-blocking tacho monitoring 18* 13(12) Rev. 4752B–INDCO–09/05 2. Pin Configuration Figure 2-1. Pinning DIP18 Isync 1 18 PB/TM 17 Vsync 16 VRef 15 OVL GND 2 VS 3 Output 4 Retr 5 VRP 6 CP 7 F/V 8 CRV 9 U211B 14 Isense 13 Csoft 12 CTR/OPO 11 OP+ 10 OP- Table 2-1. Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 Pin Description Symbol Isync GND VS Output Retr VRP CP F/V CRV OPOP+ CTR/OPO Csoft Isense OVL VRef Vsync PB/TM Function Current synchronization Ground Supply voltage Trigger pulse output Retrigger programming Ramp current adjust Ramp voltage Frequency-to-voltage converter Charge pump OP inverting input OP non-inverting input Control input/OP output Soft start Load-current sensing Overload adjust Reference voltage Voltage synchronization Pulse blocking/tacho monitoring 2 U211B 4752B–INDCO–09/05 U211B Figure 2-2. Pinning SO16 Isync GND VS Output VRP CP F/V CRV 1 2 3 4 16 V sync 15 V Ref 14 OVL 13 Isense U211B 5 6 7 8 12 Csoft 11 CTR/OPO 10 OP+ 9 OP- Table 2-2. Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 Pin Description Symbol Isync GND VS Output VRP CP F/V CRV OPOP+ CTR/OPO Csoft Isense OVL VRef Vsync Function Current synchronization Ground Supply voltage Trigger pulse output Ramp current adjust Ramp voltage Frequency-to-voltage converter Charge pump OP inverting input OP non-inverting input Control input/OP output Soft start Load-current sensing Overload adjust Reference voltage Voltage synchronization 3 4752B–INDCO–09/05 3. Mains Supply The U211B is equipped with voltage limiting and can therefore be supplied directly from the mains. The supply voltage between pin 2 (+ pol/_|_) and pin 3 builds up across D1 and R1 and is smoothed by C1. The value of the series resistance can be approximated using: VM – VS R 1 = -------------------2 IS Further information regarding the design of the mains supply can be found in the section “Design Hints” on page 9. The reference voltage source on pin 16 of typically -8.9 V is derived from the supply voltage and is used for regulation. Operation using an externally stabilized DC voltage is not recommended. If the supply cannot be taken directly from the mains because the power dissipation in R1 would be too large, the circuit as shown in Figure 3-1 should be used. Figure 3-1. Supply Voltage for High Current Requirements ~ 24 V~ 1 2 3 4 5 R1 C1 4. Phase Control The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchronized by the voltage detector) with the set value on the control input pin 12. The slope of the ramp is determined by C2 and its charging current. The charging current can be varied using R2 on pin 6. The maximum phase angle αmax can also be adjusted by using R2. When the potential on pin 7 reaches the nominal value predetermined at pin 12, a trigger pulse is generated whose width tp is determined by the value of C2 (the value of C2 and hence the pulse width can be evaluated by assuming 8 µs/nF). At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, no more pulses can be generated in that half cycle. The current sensor on pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that “gaps” in the load current are prevented. The control signal on pin 12 can be in the range of 0 V to -7 V (reference point pin 2). If V12 = -7 V, the phase angle is at maximum (αmax), i.e., the current flow angle, is at minimum. The phase angle is minimum (αmin) when V12 = V2. 4 U211B 4752B–INDCO–09/05 U211B 5. Voltage Monitoring As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. At the same time, all latches in the circuit (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply. 6. Soft Start As soon as the supply voltage builds up (t1), the integrated soft start is initiated. Figure 6-1 shows the behavior of the voltage across the soft-start capacitor, which is identical with the voltage on the phase-control input on pin 12. This behavior guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time. Figure 6-1. Soft Start VC3 V12 V0 t1 t2 t tot t3 t t1 = Build-up of supply voltage t2 = Charging of C3 to starting voltage t1 + t2 = Dead time t3 = Run-up time ttot = Total start-up time to required speed C3 is first charged up to the starting voltage V0 with a current of typically 45 µA (t2). By reducing the charging current to approximately 4 µA, the slope of the charging function is also substantially reduced, so that the rotational speed of the motor only slowly increases. The charging current then increases as the voltage across C3 increases, resulting in a progressively rising charging function which accelerates the motor more and more with increasing rotational speed. The charging function determines the acceleration up to the set point. The charging current can have a maximum value of 55 µA. 5 4752B–INDCO–09/05 7. Frequency-to-voltage Converter The internal frequency-to-voltage converter (f/V converter) generates a DC signal on pin 10 which is proportional to the rotational speed, using an AC signal from a tacho generator or a light beam whose frequency is in turn dependent on the rotational speed. The high-impedance input pin 8 compares the tacho voltage to a switch-on threshold of typically -100 mV. The switch-off threshold is -50 mV. The hysteresis guarantees very reliable operation even when relatively simple tacho generators are used. The tacho frequency is given by: n f = ----- × p (Hz) 60 where: n p = Revolutions per minute = Number of pulses per revolution The converter is based on the charge pumping principle. With each negative half-wave of the input signal, a quantity of charge determined by C5 is internally amplified and then integrated by C6 at the converter output on pin 10. The conversion constant is determined by C5, its charge transfer voltage of Vch, R6 (pin 10) and the internally adjusted charge transfer gain. I 10 G i ------ = 8.3 I9 k = Gi × C5 × R6 × Vch The analog output voltage is given by VO = k × f The values of C5 and C6 must be such that for the highest possible input frequency, the maximum output voltage V O d oes not exceed 6 V. While C 5 i s charging up, the R i o n pin 9 is approximately 6.7 kΩ. To obtain good linearity of the f/V converter, the time constant resulting from Ri and C5 should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. The amount of remaining ripple on the output voltage on pin 10 is dependent on C5, C6 and the internal charge amplification. G i × V ch × C 5 ∆ V O = -----------------------------------C6 The ripple ∆VO can be reduced by using larger values of C6. However, the increasing speed will then also be reduced. The value of this capacitor should be chosen to fit the particular control loop where it is going to be used. 6 U211B 4752B–INDCO–09/05 U211B 7.1 Pulse Blocking The output of pulses can be blocked by using pin 18 (standby operation) and the system reset via the voltage monitor if V18 ≥ -1.25 V. After cycling through the switching point hysteresis, the output is released when V18 ≤-1.5 V, followed by a soft start such as after turn-on. Monitoring of the rotation can be carried out by connecting an RC network to pin 18. In the event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is determined by R and C. The capacitor C is discharged via an internal resistance Ri = 2 kΩ with each charge transfer process of the f/V converter. If there are no more charge transfer processes, C is charged up via R until the switch-off threshold is exceeded and the triac triggering pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation, pin 18 and pin 16 must be connected together. Figure 7-1. Operation Delay C = 1 µF 10 V 18 17 16 15 R = 1 MΩ 1 2 3 4 7.2 Control Amplifier The integrated control amplifier (see Figure 10-17 on page 21) with differential input compares the set value (pin 11) with the instantaneous value on pin 10, and generates a regulating voltage on the output pin 12 (together with the external circuitry on pin 12). This pin always tries to keep the actual voltage at the value of the set voltages. The amplifier has a transmittance of typically 1000 µA/V and a bipolar current source output on pin 12 which operates with typically ±110 µA. The amplification and frequency response are determined by R7, C7, C8 and R11 (can be left out). For open-loop operation, C4, C5, R6, R7, C7, C8 and R11 can be omitted. Pin 10 should be connected with pin 12 and pin 8 with pin 2. The phase angle of the triggering pulse can be adjusted by using the voltage on pin 11. An internal limitation circuit prevents the voltage on pin 12 from becoming more negative than V16 + 1 V. 7.3 Load Limitation The load limitation, with standard circuitry, provides full protection against overloading of the motor. The function of load limiting takes account of the fact that motors operating at higher speeds can safely withstand larger power dissipations than at lower speeds due to the increased action of the cooling fan. Similarly, considerations have been made for short-term overloads for the motor which are, in practice, often required. These behaviors are not damaging and can be tolerated. 7 4752B–INDCO–09/05 In each positive half-cycle, the circuit measures, via R10, the load current on pin 14 as a potential drop across R8 and produces a current proportional to the voltage on pin 14. This current is available on pin 15 and is integrated by C9. If, following high-current amplitudes or a large phase angle for current flow, the voltage on C9 exceeds an internally set threshold of approximately 7.3 V (reference voltage pin 16), a latch is set and load limiting is turned on. A current source (sink) controlled by the control voltage on pin 15 now draws current from pin 12 and lowers the control voltage on pin 12 so that the phase angle α is increased to αmax. The simultaneous reduction of the phase angle during which current flows causes firstly a reduction of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly a reduction of the potential on C9 which in turn reduces the influence of the current sink on pin 12. The control voltage can then increase again and bring down the phase angle. This cycle of action sets up a “balanced condition” between the “current integral” on pin 15 and the control voltage on pin 12. Apart from the amplitude of the load current and the time during which current flows, the potential on pin 12 and hence the rotational speed also affects the function of load limiting. A current proportional to the potential on pin 10 gives rise to a voltage drop across R10, via pin 14, so that the current measured on pin 14 is smaller than the actual current through R8. This means that higher rotational speeds and higher current amplitudes lead to the same current integral. Therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on pin 15 is exceeded. The effect of speed on the maximum power is determined by the resistor R10 and can therefore be adjusted to suit each individual application. If, after load limiting has been turned on, the momentum of the load sinks below the “o-momentum” set using R10, V15 will be reduced. V12 can then increase again so that the phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the motor and hence the motor runs up, as long as this is allowed by the load momentum. For an already rotating machine, the effect of rotation on the measured “current integral” ensures that the power dissipation is able to increase with the rotational speed. The result is a current-controlled acceleration run-up which ends in a small peak of acceleration when the set point is reached. The load limiting latch is simultaneously reset. Then the speed of the motor is under control again and is capable of carrying its full load. The above mentioned peak of acceleration depends upon the ripple of actual speed voltage. A large amount of ripple also leads to a large peak of acceleration. The measuring resistor R8 should have a value which ensures that the amplitude of the voltage across it does not exceed 600 mV. 8 U211B 4752B–INDCO–09/05 U211B 7.4 Design Hints Practical trials are normally needed for the exact determination of the values of the relevant components for load limiting. To make this evaluation easier, the following table shows the effect of the circuitry on the important parameters for load limiting and summarizes the general tendencies. Table 7-1. Parameters Pmax Pmin Pmax/min td tr Load Limiting Parameters Component R10 Increasing Increases Increases Increases n.e. n.e. Component R9 Increasing Decreases Decreases n.e. Increases Increases Component C9 Increasing n.e. n.e. n.e. Increases Increases Pmax Pmin td tr n.e. - Maximum continuous power dissipationP1 = f(n) n ≠ 0 - Power dissipation with no rotation P1 = f(n) n = 0 - Operation delay time - Recovery time - No effect 7.5 Pulse-output Stage The pulse-output stage is short-circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function IGT = f(RGT) can be taken from Figure 10-12 on page 18. 7.6 Automatic Retriggering The variable automatic retriggering prevents half cycles without current flow, even if the triac has been turned off earlier, e.g., due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. If necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between pin 5 and pin 3 (R5-3). With the maximum repetition rate (pin 5 directly connected to pin 3), the next attempt to trigger comes after a pause of 4.5 tp and this is repeated until either the triac fires or the half cycle finishes. If pin 5 is not connected, only one trigger pulse per half cycle is generated. Since the value of R5-3 determines the charging current of C2, any repetition rate set using R5-3 is only valid for a fixed value of C2. 9 4752B–INDCO–09/05 7.7 General Hints and Explanation of Terms To ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed circuit boards. • The connecting lines from C2 to pin 7 and pin 2 should be as short as possible. The connection to pin 2 should not carry any additional high current such as the load current. When selecting C2, a low temperature coefficient is desirable. • The common (earth) connections of the set-point generator, the tacho generator and the final interference suppression capacitor C4 of the f/V converter should not carry load current. • The tacho generator should be mounted without influence by strong stray fields from the motor. • The connections from R10 and C5 should be as short as possible. To achieve a high noise immunity, a maximum ramp voltage of 6 V should be used. The typical resistance Rϕ can be calculated from Iϕ as follows: T ( ms ) × 1.13 ( V ) × 10 R ϕ( k Ω) = ------------------------------------------------------------C ( nF ) × 6 ( V ) T= Cϕ = 3 Period duration for mains frequency (10 ms at 50 Hz) Ramp capacitor, maximum ramp voltage 6 V and constant voltage drop at Rϕ = 1.13 V A 10% lower value of Rϕ (under worst case conditions) is recommended. Figure 7-2. Explanation of Terms in Phase Relationship V Mains Supply π/2 VGT Trigger Pulse VL Load Voltage tp π 3/2π 2π tpp = 4.5 tp I L Load Current Φ ϕ 10 U211B 4752B–INDCO–09/05 U211B 7.8 Design Calculations for Main Supply The following equations can be used for the evaluation of the series resistor R1 for worst case conditions: V Mmin – V Smax R 1max = 0.85 ------------------------------------2 I tot V M – V Smin R 1min = ---------------------------2 I Smax ( V Mmax – V Smin ) P ( R1max ) = --------------------------------------------2 R1 where: VM VS 2 Itot ISmax Ip Ix = Mains voltage = Supply voltage on pin 3 = Total DC current requirement of the circuit = IS + Ip + Ix = Current requirement of the IC in mA = Average current requirement of the triggering pulse = Current requirement of other peripheral components R1 can be easily evaluated from the Figure 10-14 on page 19, Figure 10-15 on page 19 and Figure 10-16 on page 20. 11 4752B–INDCO–09/05 8. Absolute Maximum Ratings Reference point pin 2, unless otherwise specified Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Parameters Current requirement t ≤10 µs Synchronization current t < 10 µs t < 10 µs f/V Converter Input current t < 10 µs Load Limiting Limiting current, negative half wave t < 10 µs Input voltage Phase Control Input voltage Input current Soft Start Input voltage Pulse Output Reverse voltage Pulse Blocking Input voltage Amplifier Input voltage Pin 9 open Reference Voltage Source Output current Storage temperature range Junction temperature Ambient temperature range 16 Io Tstg Tj Tamb 7.5 -40 to +125 125 -10 to +100 mA °C °C °C 11 10 VI -VI 0 to VS |V16| to 0 V V 18 -VI |V16| to 0 V 4 VR VS to 5 V 13 -VI |V16| to 0 V 12 12 6 -VI ±II -II 0 to 7 500 1 V µA mA 14 14 14 15 II II ±Vi -VI 5 35 1 |V16| to 0 mA mA V V 8 8 II ±iI 3 13 mA mA Pins 3 3 1 17 1 17 Symbol -IS -is IsyncI IsyncV ±iI ±iI Value 30 100 5 5 35 35 Unit mA mA mA mA mA mA 12 U211B 4752B–INDCO–09/05 U211B 9. Thermal Resistance Parameters Junction ambient DIP18 SO16 on p.c. SO16 on ceramic Symbol RthJA RthJA RthJA Value 120 180 100 Unit K/W K/W K/W 10. Electrical Characteristics -VS = 13.0 V, Tamb = 25° C, reference point pin 2, unless otherwise specified Parameters Supply voltage for mains operation Supply voltage limitation DC current requirement Reference voltage source Temperature coefficient Voltage Monitoring Turn-on threshold Turn-off threshold Phase-control Currents Synchronization current Voltage limitation ±IL = 5 mA I7 = f(R6) R6 = 50 kΩ to 1 MΩ α ≥ 180° 1 17 1, 17 ±IsyncI ±IsyncV ±VI 0.35 1.4 1.6 2.0 1.8 mA V 3 3 -VSON -VSOFF 11.2 9.9 13.0 10.9 V V -IS = 4 mA -IS = 30 mA -VS = 13.0 V -IL = 10 µA -IL = 5 mA Test Conditions Pins 3 3 3 16 16 Symbol -VS -VS IS -VRef -TCVRef Min. 13.0 14.6 14.7 1.2 8.6 8.3 2.5 8.9 0.5 Typ. Max. VLimit 16.6 16.8 3.0 9.2 9.1 Unit V V V mA V V mV/K Reference Ramp (see Figure 10-1 on page 15) Charge current Rϕ-reference voltage Temperature coefficient Pulse Output (see Figure 10-12 on page 18, Pin 4) Output pulse current Reverse current Output pulse width Amplifier Common-mode signal range Input bias current Input offset voltage Output current Short circuit forward, transmittance I12 = f(V10-11), (see Figure 10-7 on page 17) 10, 11 11 10, 11 12 12 V10, V11 IIO V10 -IO +IO Yf 75 88 V16 0.01 10 110 120 1000 145 165 -1 1 V µA mV µA µA µA/V Cϕ = 10 nF RGT = 0, VGT = 1.2 V Io Ior tp 100 155 0.01 80 190 3.0 mA µA µs 7 6, 3 6 I7 VϕRef TCVϕRef 1 1.06 20 1.13 0.5 1.18 µA V mV/K 13 4752B–INDCO–09/05 10. Electrical Characteristics (Continued) -VS = 13.0 V, Tamb = 25° C, reference point pin 2, unless otherwise specified Parameters Pulse Blocking, Tacho Monitoring Logic-on Logic-off Input current Output resistance Frequency-to-voltage Converter Input bias current II = -1 mA II = +1 mA (see Figure 10-7 on page 17) 8 IIB -VI +VI 660 7.25 0.6 2 750 8.05 µA mV V V18 = VTOFF = 1.25 V V18 = V16 18 18 18 18 -VTON -VTOFF II RO 14.5 1.5 6 10 3.7 1.5 1.25 0.3 1.0 1 V V µA µA kΩ Test Conditions Pins Symbol Min. Typ. Max. Unit Input voltage limitation 8 Turn-on threshold Turn-off threshold Charge Amplifier Discharge current Charge transfer voltage Charge transfer gain Conversion factor Output operating range Linearity I10/I9 C5 = 1 nF, R6 = 100 kΩ (see Figure 10-17 on page 21) C5 = 1 nF, (see Figure 10-17 on page 21) 8 8 -VTON -VTOFF 20 100 50 150 mV mV 9 9 to 16 9, 10 Idis Vch Gi K 6.50 7.5 0.5 6.70 8.3 5.5 0-6 ±1 6.90 9.0 mA V mV/Hz V % 55 130 7 80 10 6 µA µA µA µA mA tp tp +1.0 V µA µA µA µA V 10 to 16 VO Soft Start, f/V Converter Non-active (see Figure 10-2 on page 15 and Figure 10-4 on page 16) Starting current Final current Starting current Final current Discharge current Repetition rate V13 = V16, V8 = V2 V13 = 0.5 V13 = V16 V13 = 0.5 Restart pulse R5-3 = 0 R5-3 = 15 kΩ Operating voltage range Offset current Input current Output current Overload ON V10 = V16 V14 = V2 via 1 kΩ V10 = 4.5 V V14 = 300 mV 14 14 15-16 14 15-16 15-16 13 13 13 13 IO IO IO IO IO tpp tpp VI IO IO II IO VTON -1.0 5 0.1 60 110 7.05 7.4 90 20 50 2 30 0.5 3 45 85 4 55 3 4.5 20 f/V Converter Active (see Figure 10-3 on page 15, Figure 10-5 on page 16 and Figure 10-6 on page 16) Automatic Retriggering (see Figure 10-13 on page 19, Pin 5) Load Limiting (see Figure 10-9 on page 17, Figure 10-10 on page 18 and Figure 10-11 on page 18) 12 1.0 120 140 7.7 14 U211B 4752B–INDCO–09/05 U211B Figure 10-1. Ramp Control 240 Reference Point Pin 2 200 Phase Angle α (°) 10nF 160 4.7nF 2.2nF 120 80 Cϕ/t =1.5nF /t 0 0 0.2 0.4 0.6 0.8 1.0 Rϕ (MΩ) Figure 10-2. Soft-start Charge Current (f/V Converter Non-active) 100 80 I13 (µA) 60 40 20 Reference Point Pin 16 0 0 2 4 V13 (V) 6 8 10 Figure 10-3. Soft-start Charge Current (f/V Converter Active) 100 80 Reference Point Pin 16 I13 (µA) 60 40 20 0 0 2 4 V13 (V) 6 8 10 15 4752B–INDCO–09/05 Figure 10-4. Soft-start Voltage (f/V Converter Non-active) 10 8 V13 (V) 6 4 2 Reference Point Pin 16 0 t = f(C3) Figure 10-5. Soft-start Voltage (f/V Converter Active) 10 8 Reference Point Pin 16 V13 (V) 6 4 2 0 t = f(C3) Figure 10-6. Soft-start Function 10 8 6 4 2 0 t = f(C3) Motor Standstill (Dead Time) Motor in Action Reference Point Pin 16 16 U211B 4752B–INDCO–09/05 V13 (V) U211B Figure 10-7. f/V Converter Voltage Limitation 500 250 I8 (µA) Reference Point Pin 2 0 -250 -500 -10 -8 -6 -4 -2 0 2 4 V8 (V) Figure 10-8. Amplifier Output Characteristics 100 50 I12 (µA) 0 -50 Reference Point for I12 = -4 V -200 -100 0 100 200 300 -100 -300 V10-11 (V) Figure 10-9. Load Limit Control 200 150 -I12-16 (µA) 100 50 0 0 2 4 V15-16 (V) 6 8 17 4752B–INDCO–09/05 Figure 10-10. Load Limit Control f/V Dependency 200 150 I14-2 (µA) 100 50 0 0 2 4 V10-16 (V) 6 8 Figure 10-11. Load Current Detection 250 200 I15-16 (µA) 150 100 I15 = f(VShunt) V10 = V16 50 0 0 100 200 300 400 500 600 700 V14-2 (mV) Figure 10-12. Pulse Output 100 80 IGT (mA) 60 40 1.4 V 20 VGT = 0.8 V 0 0 200 400 600 800 1000 RGT (Ω) 18 U211B 4752B–INDCO–09/05 U211B Figure 10-13. Automatic Retriggering Repetition Rate 20 15 R5-3 (kΩ) 10 5 0 0 6 12 tpp/tp 18 24 30 Figure 10-14. Determination of R1 50 40 Mains Supply 230 V R1 (kΩ) 30 20 10 0 0 4 8 Itot (mA) 12 16 Figure 10-15. Power Dissipation of R1 6 5 4 P(R1) (W) Mains Supply 230 V 3 2 1 0 0 10 20 R1 (kΩ) 30 40 19 4752B–INDCO–09/05 Figure 10-16. Power Dissipation of R1 According to Current Consumption 6 5 4 P(R1) (W) Mains Supply 230 V 3 2 1 0 0 3 6 Itot (mA) 9 12 15 20 U211B 4752B–INDCO–09/05 1N4007 D1 R1 M L 18 k Ω 2W R4 470 k Ω 1 Voltage/current detector Output pulse 180 Ω 6 7 3 2 -V C2 S 4752B–INDCO–09/05 R13 R3 220 kΩ 17 Automatic retriggering R2 3.3 nF 1 MΩ R8 33 mΩ 1W 4 R 12 TIC 226 5 47 k Ω R31 100 k Ω Set speed voltage VM = 230 V ~ R14 56 k Ω Control amplifier R19 100 k Ω C 10 + 11 2.2 µF/16V 10 Phasecontrol unit ϕ = f (V12 ) Supply voltage limitation Reference voltage Voltage monitoring 16 C1 GND C 11 22 µF/ 25 V 2.2 µF N R 10 1 kΩ Load limitation speed/time controlled 14 1 MΩ R9 Figure 10-17. Speed Control, Automatic Retriggering, Load Limiting, Soft Start C9 Controlled current sink Soft start -VRef 12 R11 2 MΩ R6 100 k Ω 22 k Ω R7 10 µF/16V C3 C7 C8 220 nF C5 1 nF 2.2 µF/ 16 V 13 9 8 15 4.7 µF/16V Frequencyto-voltage converter Pulse blocking tacho monitoring 18 220 nF C4 1 kΩ Speed sensor R5 Actual speed voltage C6 100 nF U211B 21 Figure 10-18. Speed Control, Automatic Retriggering, Load Switch-off, Soft Start Set speed voltage 2.2 µ F 10 V R13 250 k Ω 47 k Ω R31 100 nF 2.2 µF/10 V C10 R7 15 k Ω C5 680 pF R6 C6 C4 220 nF C7 1 MΩ 220 nF 13 6 R2 2.2 µF 10 V U211B 4.7µ F 10 V 14 15 C9 4 5 16 R9 470 k Ω 3 17 10 kΩ R14 2 GND -V S 1 MΩ 2.2 µ F 470 k Ω 220 k Ω R3 C11 T2 R4 180 Ω 18 1 R12 2.2 nF C ϕ/t 12 C3 7 C8 Rϕ C2 47 kΩ 1N4004 D1 R1 18 k Ω 1.5 W T1 R15 BZX55 47 k Ω R16 C1 N 4752B–INDCO–09/05 22 µF 25 V R8= 3 x 11 m Ω 1W R10 2.2 k Ω M The switch-off level at maximum load shows in principle the same speed dependency as the original version (see Figure 10-17 on page 21), but when reaching the maximum load, the motor is switched off completely. This function is effected by the thyristor (formed by T1 and T2) which ignites when the voltage at pin 15 reaches typically 7.4 V (reference point pin 16). The circuit is thereby switched to standby mode over the release Pin 18. 22 U211B 230 V~ L Speed sensor 10 9 100 k Ω R11 11 8 R5 1 kΩ U211B Figure 10-19. Speed Control, Automatic Retriggering, Load Switch-down, Soft Start Set speed voltage 2.2 µF 10 V R13 47 k Ω R31 100 nF 250 k Ω 2.2 µ F/ 10 V R7 15 k Ω 680 pF R6 C4 220 nF C10 C7 C5 100 k Ω 220 nF 1 MΩ 13 U211B 6 4.7µ F 10 V 2.2 µ F 10 V 14 15 C9 4 5 16 2.2 µF C 11 3 17 2 GND -V S R2 1 MΩ R9 470 k Ω R14 10 kΩ 18 k Ω 1.5 W R4 470 k Ω 220 k Ω R3 180 Ω 18 1 R12 C2 2.2 nF C ϕ/t 12 C8 C3 7 Rϕ 33 k Ω R15 T2 1N4004 D1 R1 T1 C1 230 V~ N R8 = 3 x 11 m Ω 1W 47 k Ω R16 BZX55 The maximum load regulation shows in principle the same speed dependency as the original version (see Figure 10-17 on page 21). When reaching the maximum load, the control unit is turned to αmax, adjustable with R2. Then, only IO flows. This function is effected by the thyristor, formed by T1 and T2 which ignites as soon as the voltage at pin 15 reaches approximately 6.8 V (reference point pin 16). The potential at pin 15 is lifted and kept by R14 over the internal operating threshold whereby the maximum load regulation starts and adjusts the control unit constantly to αmax (IO), inspite of a reduced load current. The motor shows that the circuit is still in operation by produceing a buzzing sound. L R10 2.2 k Ω M 22 µ F 25 V Speed sensor C6 10 9 R 11 11 8 R5 1 kΩ 23 4752B–INDCO–09/05 Figure 10-20. Speed Control, Automatic Retriggering, Load Limiting, Soft Start, Tacho Control 24 C 11 C8 68 k Ω R6 C6 R11 C3 1.5 M Ω C7 1m F / 10 V 100 nF R31 250 k Ω Set speed voltage 2.2 µF 10 V 1MW 220 k W R3 18 17 14 16 13 12 15 11 10 C 10 220 nF 22 nF C9 4.7µ F R9 1 MΩ 2.2 µ F 10 V 2.2 µF /10 V R 13 47 k Ω D1 1N4004 R7 22 k Ω U211B U211B R1 1 2 3 4 -V S 5 R2 1 MΩ Rϕ C2 2.2 nF C ϕ/t R5 1 kΩ C5 GND R12 220 Ω C1 22 µF 25 V Speed sensor R4 470 k W 18 k Ω 1.5 W 6 7 8 9 1 nF C4 220 nF L R10 1 kΩ 230 V~ M N R8 = 3 x 11 m Ω 1W 4752B–INDCO–09/05 4752B–INDCO–09/05 C4 220 nF 4.7 µ F 10 V R18 Set speed min. R31 100 k Ω 10 µ F C8 C7 470 nF 1N4004 10 V R13 R11 16 k Ω Set speed max. R8 47 k Ω 2.2 µ F 10 V C11 22 nF 220 k Ω R4 18 17 16 15 14 13 12 11 10 D1 R7 470 k Ω C3 C13 all diodes BYW83 L1 M L2 R1 1 4 -V S R2 R6 R3 4.7 k Ω 1 MΩ Rϕ C2 C ϕ/t 3.3 nF R10 100 W 7 R5 GND 470 k Ω 2 3 5 6 18 k Ω 1.5 W 8 U211B CNY 70 9 C6 680 pF 230 V~ 100 Ω Figure 10-21. Speed Control with Reflective Opto Coupler CNY70 as Emitter R14 I GT = 50 mA C1 47 µ F 25 V C12 R9 220 k Ω C5 1.5 k Ω 470 nF 100 Ω R17 R16 470 Ω 150 nF 250 V~ 1N4004 ca. 220 Pulses/Revolution D2 3.5 k Ω / 8 W R 15 C10 100 µ F 10 V Z3 BZX55 C9V1 U211B 25 Figure 10-22. Speed Control, Maximum Load Control with Reflective Opto Coupler CNY70 as Emitter 26 C9 C6 470 nF 47 µ F 10 V R 14 Set speed min. R 31 220 k Ω 10 µF 110 k Ω C7 C8 17 16 13 12 14 11 10 470 nF 1N4004 15 R3 18 R13 R7 16 k Ω Set speed max. C 10 R9 220 kΩ C 11 22 nF R11 820 k Ω 2.2 µF 10 V C3 4.7 µF 10 V R6 82 k Ω U211B U211B R1 1 2 4 -V S R2 R12 1 MΩ Rϕ C2 C ϕ /t 3.3 nF 680 pF 10 k Ω R16 R5 2.2 k Ω C4 1 nF 1 µF C 13 9V 100 Ω 7 GND R4 220 k Ω 3 5 6 10 k Ω 1.1 W 8 9 C5 CNY 70 I GT = 50 mA C1 22 µF 25 V R17 33 k Ω R 18 470Ω R10 1.1 k Ω D1 230 V~ M 150 nF 250 V~ 100 Ω C12 R 8= 3 x 0.1 Ω 4752B–INDCO–09/05 U211B The schematic diagram (see Figure 10-22 on page 26) is designed as a speed control IC based on the reflection-coupled principle with 4 periods per revolution and a maximum speed of 30000 rpm. The separation of the coupler from the rotating aperture should be about approximately 1 mm. In the schematic diagram, the power supply for the coupler was provided externally because of the relatively high current consumption. Instructions for adjusting: 1. In the initial adjustment of the phase-control circuit, R2 should be adjusted so that when R14 = 0 and R31 are in minimum position, the motor just turns. 2. The speed can now be adjusted as desired by means of R31 between the limits determined by R13 and R14. 3. The switch-off power of the limiting-load control can be set by R9. The lower R9, the higher the switch-off power. 27 4752B–INDCO–09/05 11. Ordering Information Extended Type Number U211B-xY U211B-xFPY U211B-xFPG3Y Package DIP18 SO16 SO16 Remarks Tube Tube Taped and reeled 12. Package Information Package DIP18 Dimensions in mm 23.3 max 7.77 7.47 4.8 max 6.4 max 0.5 min 3.3 1.64 1.44 20.32 18 10 0.58 0.48 0.36 max 9.8 8.2 2.54 technical drawings according to DIN specifications 1 9 Package SO16 Dimensions in mm 10.0 9.85 5.2 4.8 3.7 1.4 0.4 1.27 8.89 16 9 0.25 0.10 0.2 3.8 6.15 5.85 technical drawings according to DIN specifications 1 8 28 U211B 4752B–INDCO–09/05 U211B 13. Revision History Please note that the following page numbers referred to in this section refer to the specific revision mentioned, not to this document. Revision No. 4752B-INDCO-08/05 History • Put datasheet in a new template • First page: Pb-free logo added • Page 28: Ordering Information changed 29 4752B–INDCO–09/05 Atmel Corporation 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 487-2600 Atmel Operations Memory 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 436-4314 RF/Automotive Theresienstrasse 2 Postfach 3535 74025 Heilbronn, Germany Tel: (49) 71-31-67-0 Fax: (49) 71-31-67-2340 1150 East Cheyenne Mtn. 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