LMP2011MFX

LMP2011 Single/LMP2012 Dual High Precision, Rail-to-Rail Output Operational Amplifier July 1, 2008 LMP2011 Single/LMP2012 Dual High Precision, Rail-to-Rail Output Operational Amplifier General Description The LMP201x series are the first members of National's new LMPTM precision amplifier family. The LMP201X series offers unprecedented accuracy and stability in space-saving miniature packaging while also being offered at an affordable price. This device utilizes patented techniques to measure and continually correct the input offset error voltage. The result is an amplifier which is ultra stable over time and temperature. It has excellent CMRR and PSRR ratings, and does not exhibit the familiar 1/f voltage and current noise increase that plagues traditional amplifiers. The combination of the LMP201X characteristics makes it a good choice for transducer amplifiers, high gain configurations, ADC buffer amplifiers, DAC I-V conversion, and any other 2.7V-5V application requiring precision and long term stability. Other useful benefits of the LMP201X are rail-to-rail output, a low supply current of 930 µA, and wide gain-bandwidth product of 3 MHz. These extremely versatile features found in the LMP201X provide high performance and ease of use. Features (For VS = 5V, Typical unless otherwise noted) ■ Low guaranteed VOS over temperature ■ Low noise with no 1/f ■ High CMRR ■ High PSRR ■ High AVOL ■ Wide gain-bandwidth product ■ High slew rate ■ Low supply current ■ Rail-to-rail output ■ No external capacitors required 60 µV 35nV/√Hz 130 dB 120 dB 130 dB 3MHz 4V/µs 930µA 30mV Applications ■ Precision instrumentation amplifiers ■ Thermocouple amplifiers ■ Strain gauge bridge amplifier Connection Diagrams 5-Pin SOT23 8-Pin SOIC 8-Pin MSOP 20071502 20071538 20071542 Top View Top View Top View Ordering Information Package Part Number LMP2011MF LMP2011MFX LMP2012MM LMP2012MMX LMP2011MA 8-Pin SOIC LMP2011MAX LMP2012MA LMP2012MAX −40°C to 125°C LMP2011MA LMP2012MA Temperature Range Package Marking Transport Media 1k Units Tape and Reel 3k Units Tape and Reel 1k Units Tape and Reel 3.5k Units Tape and Reel 95 Units/Rail 2.5k Units Tape and Reel 95 Units/Rail 2.5k Units Tape and Reel M08A NSC Drawing 5-Pin SOT23 8-Pin MSOP AN1A AP1A MF05A MUA08A © 2008 National Semiconductor Corporation 200715 www.national.com LMP2011 Single/LMP2012 Dual Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. ESD Tolerance Human Body Model Machine Model Supply Voltage Common-Mode Input Voltage Lead Temperature (soldering 10 sec.) 2000V 200V 5.8V −0.3 ≤ VCM ≤ VCC +0.3V +300°C Differential Input Voltage Current at Input Pin Current at Output Pin Current at Power Supply Pin ±Supply Voltage 30 mA 30 mA 50 mA (Note 1) 2.7V to 5.25V −65°C to 150°C −40°C to 125°C Operating Ratings Supply Voltage Storage Temperature Range Operating Temperature Range 2.7V DC Electrical Characteristics Symbol VOS Parameter Input Offset Voltage (LMP2011 only) Input Offset Voltage (LMP2012 only) Offset Calibration Time TCVOS Input Offset Voltage Long-Term Offset Drift Lifetime VOS Drift IIN IOS RIND CMRR Input Current Input Offset Current Input Differential Resistance Common Mode Rejection Ratio Unless otherwise specified, all limits guaranteed for TJ = 25°C, V+ = 2.7V, V− = 0V, V CM = 1.35V, VO = 1.35V and RL > 1 MΩ. Boldface limits apply at the temperature extremes. Conditions Min (Note 3) Typ (Note 2) 0.8 0.8 0.5 0.015 0.006 2.5 -3 6 9 −0.3 ≤ VCM ≤ 0.9V 0 ≤ VCM ≤ 0.9V 95 90 95 90 RL = 10 kΩ RL = 2 kΩ VO Output Swing (LMP2011 only) RL = 10 kΩ to 1.35V VIN(diff) = ±0.5V 95 90 90 85 2.665 2.655 130 Max (Note 3) 25 60 36 60 10 12 Units μV ms μV/°C μV/month μV pA pA MΩ dB PSRR AVOL Power Supply Rejection Ratio Open Loop Voltage Gain 120 130 124 2.68 0.033 0.060 0.075 dB dB V RL = 2 kΩ to 1.35V VIN(diff) = ±0.5V 2.630 2.615 2.65 0.061 0.085 0.105 V Output Swing (LMP2012 only) RL = 10 kΩ to 1.35V VIN(diff) = ±0.5V 2.64 2.63 2.68 0.033 0.060 0.075 V RL = 2 kΩ to 1.35V VIN(diff) = ±0.5V 2.615 2.6 2.65 0.061 0.085 0.105 V www.national.com 2 LMP2011 Single/LMP2012 Dual Symbol IO Parameter Output Current Conditions Sourcing, VO = 0V VIN(diff) = ±0.5V Sinking, VO = 5V VIN(diff) = ±0.5V Min (Note 3) 5 3 5 3 Typ (Note 2) 12 18 0.919 Max (Note 3) Units mA IS Supply Current per Channel 1.20 1.50 mA 2.7V AC Electrical Characteristics MΩ. Boldface limits apply at the temperature extremes. Parameter Gain-Bandwidth Product Slew Rate Phase Margin Gain Margin Input-Referred Voltage Noise Input-Referred Current Noise Input-Referred Voltage Noise Input Overload Recovery Time Symbol GBW SR θm Gm en in enp-p trec TJ = 25°C, V+ = 2.7V, V− = 0V, VCM = 1.35V, VO = 1.35V, and RL > 1 Conditions Min (Note 3) Typ (Note 2) 3 4 60 −14 35 Max (Note 3) Units MHz V/μs Deg dB nV/ pA/ nVpp ms RS = 100Ω, DC to 10 Hz 850 50 5V DC Electrical Characteristics Symbol VOS Parameter Input Offset Voltage (LMP2011 only) Input Offset Voltage (LMP2012 only) Offset Calibration Time TCVOS Input Offset Voltage Long-Term Offset Drift Lifetime VOS Drift IIN IOS RIND CMRR Input Current Input Offset Current Input Differential Resistance Common Mode Rejection Ratio Unless otherwise specified, all limits guaranteed for TJ = 25°C, V+ = 5V, V− = 0V, V CM = 2.5V, VO = 2.5V and RL > 1MΩ. Boldface limits apply at the temperature extremes. Conditions Min (Note 3) Typ (Note 2) 0.12 0.12 0.5 0.015 0.006 2.5 -3 6 9 −0.3 ≤ VCM ≤ 3.2 0 ≤ VCM ≤ 3.2 100 90 95 90 RL = 10 kΩ RL = 2 kΩ 105 100 95 90 130 Max (Note 3) 25 60 36 60 10 12 Units μV ms μV/°C μV/month μV pA pA MΩ dB PSRR AVOL Power Supply Rejection Ratio Open Loop Voltage Gain 120 130 132 dB dB 3 www.national.com LMP2011 Single/LMP2012 Dual Symbol VO Parameter Output Swing (LMP2011 only) Conditions RL = 10 kΩ to 2.5V VIN(diff) = ±0.5V Min (Note 3) 4.96 4.95 Typ (Note 2) 4.978 0.040 Max (Note 3) Units 0.070 0.085 V RL = 2 kΩ to 2.5V VIN(diff) = ±0.5V 4.895 4.875 4.919 0.091 0.115 0.140 V Output Swing (LMP2012 only) RL = 10 kΩ to 2.5V VIN(diff) = ±0.5V 4.92 4.91 4.978 0.040 0.080 0.095 V RL = 2 kΩ to 2.5V VIN(diff) = ±0.5V 4.875 4.855 4.919 0.0.91 0.125 0.150 V IO Output Current Sourcing, VO = 0V VIN(diff) = ±0.5V Sinking, VO = 5V V IN(diff) = ±0.5V 8 6 8 6 15 17 0.930 1.20 1.50 mA IS Supply Current per Channel mA 5V AC Electrical Characteristics Boldface limits apply at the temperature extremes. Symbol GBW SR θm Gm en in enp-p trec Parameter Gain-Bandwidth Product Slew Rate Phase Margin Gain Margin Input-Referred Voltage Noise Input-Referred Current Noise Input-Referred Voltage Noise Input Overload Recovery Time TJ = 25°C, V+ = 5V, V− = 0V, VCM = 2.5V, VO = 2.5V, and RL > 1MΩ. Conditions Min (Note 3) Typ (Note 2) 3 4 60 −15 35 Max (Note 3) Units MHz V/μs deg dB nV/ pA/ nVpp ms RS = 100Ω, DC to 10 Hz 850 50 Note 1: Absolute Maximum Ratings indicate limits beyond which damage may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and test conditions, see the Electrical Characteristics. Note 2: Typical values represent the most likely parametric norm. Note 3: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using statistical quality control (SQC) method. www.national.com 4 LMP2011 Single/LMP2012 Dual Typical Performance Characteristics Supply Current vs. Supply Voltage TA=25C, VS= 5V unless otherwise specified. Offset Voltage vs. Supply Voltage 20071555 20071556 Offset Voltage vs. Common Mode Offset Voltage vs. Common Mode 20071557 20071558 Voltage Noise vs. Frequency Input Bias Current vs. Common Mode 20071504 20071503 5 www.national.com LMP2011 Single/LMP2012 Dual PSRR vs. Frequency PSRR vs. Frequency 20071507 20071506 Output Sourcing @ 2.7V Output Sourcing @ 5V 20071559 20071560 Output Sinking @ 2.7V Output Sinking @ 5V 20071561 20071562 www.national.com 6 LMP2011 Single/LMP2012 Dual Max Output Swing vs. Supply Voltage Max Output Swing vs. Supply Voltage 20071563 20071564 Min Output Swing vs. Supply Voltage Min Output Swing vs. Supply Voltage 20071565 20071566 CMRR vs. Frequency Open Loop Gain and Phase vs. Supply Voltage 20071505 20071508 7 www.national.com LMP2011 Single/LMP2012 Dual Open Loop Gain and Phase vs. RL @ 2.7V Open Loop Gain and Phase vs. RL @ 5V 20071509 20071510 Open Loop Gain and Phase vs. CL @ 2.7V Open Loop Gain and Phase vs. CL @ 5V 20071511 20071512 Open Loop Gain and Phase vs. Temperature @ 2.7V Open Loop Gain and Phase vs. Temperature @ 5V 20071536 20071537 www.national.com 8 LMP2011 Single/LMP2012 Dual THD+N vs. AMPL THD+N vs. Frequency 20071514 20071513 0.1 Hz − 10 Hz Noise vs. Time 20071515 9 www.national.com LMP2011 Single/LMP2012 Dual Application Information THE BENEFITS OF LMP201X NO 1/f NOISE Using patented methods, the LMP201X eliminates the 1/f noise present in other amplifiers. That noise, which increases as frequency decreases, is a major source of measurement error in all DC-coupled measurements. Low-frequency noise appears as a constantly-changing signal in series with any measurement being made. As a result, even when the measurement is made rapidly, this constantly-changing noise signal will corrupt the result. The value of this noise signal can be surprisingly large. For example: If a conventional amplifier and a noise corner of has a flat-band noise level of 10nV/ 10 Hz, the RMS noise at 0.001 Hz is 1µV/ . This is equivalent to a 0.50 µV peak-to-peak error, in the frequency range 0.001 Hz to 1.0 Hz. In a circuit with a gain of 1000, this produces a 0.50 mV peak-to-peak output error. This number of 0.001 Hz might appear unreasonably low, but when a data acquisition system is operating for 17 minutes, it has been on long enough to include this error. In this same time, the LMP201X will only have a 0.21 mV output error. This is smaller by 2.4 x. Keep in mind that this 1/f error gets even larger at lower frequencies. At the extreme, many people try to reduce this error by integrating or taking several samples of the same signal. This is also doomed to failure because the 1/f nature of this noise means that taking longer samples just moves the measurement into lower frequencies where the noise level is even higher. The LMP201X eliminates this source of error. The noise level is constant with frequency so that reducing the bandwidth reduces the errors caused by noise. Another source of error that is rarely mentioned is the error voltage caused by the inadvertent thermocouples created when the common "Kovar type" IC package lead materials are soldered to a copper printed circuit board. These steel-based leadframe materials can produce over 35 μV/°C when soldered onto a copper trace. This can result in thermocouple noise that is equal to the LMP201X noise when there is a temperature difference of only 0.0014°C between the lead and the board! For this reason, the lead-frame of the LMP201X is made of copper. This results in equal and opposite junctions which cancel this effect. The extremely small size of the SOT-23 package results in the leads being very close together. This further reduces the probability of temperature differences and hence decreases thermal noise. OVERLOAD RECOVERY The LMP201X recovers from input overload much faster than most chopper-stabilized op amps. Recovery from driving the amplifier to 2X the full scale output, only requires about 40 ms. Many chopper-stabilized amplifiers will take from 250 ms to several seconds to recover from this same overload. This is because large capacitors are used to store the unadjusted offset voltage. 20071516 FIGURE 1. Overload Recovery Test The wide bandwidth of the LMP201X enhances performance when it is used as an amplifier to drive loads that inject transients back into the output. ADCs (Analog-to-Digital Converters) and multiplexers are examples of this type of load. To simulate this type of load, a pulse generator producing a 1V peak square wave was connected to the output through a 10 pF capacitor. (Figure 1) The typical time for the output to recover to 1% of the applied pulse is 80 ns. To recover to 0.1% requires 860ns. This rapid recovery is due to the wide bandwidth of the output stage and large total GBW. NO EXTERNAL CAPACITORS REQUIRED The LMP201X does not need external capacitors. This eliminates the problems caused by capacitor leakage and dielectric absorption, which can cause delays of several seconds from turn-on until the amplifier's error has settled. MORE BENEFITS The LMP201X offers the benefits mentioned above and more. It has a rail-to-rail output and consumes only 950 µA of supply current while providing excellent DC and AC electrical performance. In DC performance, the LMP201X achieves 130 dB of CMRR, 120 dB of PSRR and 130 dB of open loop gain. In AC performance, the LMP201X provides 3 MHz of gainbandwidth product and 4 V/µs of slew rate. HOW THE LMP201X WORKS The LMP201X uses new, patented techniques to achieve the high DC accuracy traditionally associated with chopper-stabilized amplifiers without the major drawbacks produced by chopping. The LMP201X continuously monitors the input offset and corrects this error. The conventional chopping process produces many mixing products, both sums and differences, between the chopping frequency and the incoming signal frequency. This mixing causes large amounts of distortion, particularly when the signal frequency approaches the chopping frequency. Even without an incoming signal, the chopper harmonics mix with each other to produce even more trash. If this sounds unlikely or difficult to understand, look at the plot (Figure 2), of the output of a typical (MAX432) chopper-stabilized op amp. This is the output when there is no incoming signal, just the amplifier in a gain of -10 with the input grounded. The chopper is operating at about 150 Hz; the rest is mixing products. Add an input signal and the noise gets much worse. Compare this plot with Figure 3 of the LMP201X. This data was taken under the exact same conditions. The auto-zero action is visible at about 30 kHz but note the absence of mixing products at other frequencies. As a result, the LMP201X has very low distortion of 0.02% and very low mixing products. www.national.com 10 LMP2011 Single/LMP2012 Dual PRECISION STRAIN-GAUGE AMPLIFIER This Strain-Gauge amplifier (Figure 4) provides high gain (1006 or ~60 dB) with very low offset and drift. Using the resistors' tolerances as shown, the worst case CMRR will be greater than 108 dB. The CMRR is directly related to the resistor mismatch. The rejection of common-mode error, at the output, is independent of the differential gain, which is set by R3. The CMRR is further improved, if the resistor ratio matching is improved, by specifying tighter-tolerance resistors, or by trimming. 20071517 FIGURE 2. The Output of a Chopper Stabilized Op Amp (MAX432) 20071518 FIGURE 4. Precision Strain Gauge Amplifier Extending Supply Voltages and Output Swing by Using a Composite Amplifier Configuration: In cases where substantially higher output swing is required with higher supply voltages, arrangements like the ones shown in Figure 5 and Figure 6 could be used. These configurations utilize the excellent DC performance of the LMP201X while at the same time allow the superior voltage and frequency capabilities of the LM6171 to set the dynamic performance of the overall amplifier. For example, it is possible to achieve ±12V output swing with 300 MHz of overall GBW (AV = 100) while keeping the worst case output shift due to VOS less than 4 mV. The LMP201X output voltage is kept at about mid-point of its overall supply voltage, and its input common mode voltage range allows the V- terminal to be grounded in one case (Figure 5, inverting operation) and tied to a small non-critical negative bias in another (Figure 6, noninverting operation). Higher closed-loop gains are also possible with a corresponding reduction in realizable bandwidth. Table 1 shows some other closed loop gain possibilities along with the measured performance in each case. 20071504 FIGURE 3. The Output of the LMP2011/LMP2012 INPUT CURRENTS The LMP201X's input currents are different than standard bipolar or CMOS input currents in that it appears as a current flowing in one input and out the other. Under most operating conditions, these currents are in the picoamp level and will have little or no effect in most circuits. These currents tend to increase slightly when the common-mode voltage is near the minus supply. (See the typical curves.) At high temperatures such as 85°C, the input currents become larger, 0.5 nA typical, and are both positive except when the VCM is near V−. If operation is expected at low common-mode voltages and high temperature, do not add resistance in series with the inputs to balance the impedances. Doing this can cause an increase in offset voltage. A small resistance such as 1 kΩ can provide some protection against very large transients or overloads, and will not increase the offset significantly. 11 www.national.com LMP2011 Single/LMP2012 Dual It should be kept in mind that in order to minimize the output noise voltage for a given closed-loop gain setting, one could minimize the overall bandwidth. As can be seen from Equation 1 above, the output noise has a square-root relationship to the Bandwidth. In the case of the inverting configuration, it is also possible to increase the input impedance of the overall amplifier, by raising the value of R1, without having to increase the feed-back resistor, R2, to impractical values, by utilizing a "Tee" network as feedback. See the LMC6442 data sheet (Application Notes section) for more details on this. 20071519 FIGURE 5. Composite Amplifier Configuration 20071521 TABLE 1. Composite Amplifier Measured Performance AV 50 100 100 500 1000 R1 (Ω) 200 100 1k 200 100 R2 (Ω) 10k 10k 100k 100k 100k C2 (pF) 8 10 0.67 1.75 2.2 BW (MHz) 3.3 2.5 3.1 1.4 0.98 SR en p-p (V/μs) (mVPP) 178 174 170 96 64 37 70 70 250 400 FIGURE 7. AC Coupled ADC Driver LMP201X AS ADC INPUT AMPLIFIER The LMP201X is a great choice for an amplifier stage immediately before the input of an ADC (Analog-to-Digital Converter), whether AC or DC coupled. See Figure 7 and Figure 8. This is because of the following important characteristics: A) Very low offset voltage and offset voltage drift over time and temperature allow a high closed-loop gain setting without introducing any short-term or long-term errors. For example, when set to a closed-loop gain of 100 as the analog input amplifier for a 12-bit A/D converter, the overall conversion error over full operation temperature and 30 years life of the part (operating at 50°C) would be less than 5 LSBs. B) Fast large-signal settling time to 0.01% of final value (1.4 μs) allows 12 bit accuracy at 100 KHZ or more sampling rate. C) No flicker (1/f) noise means unsurpassed data accuracy over any measurement period of time, no matter how long. Consider the following op amp performance, based on a typical low-noise, high-performance commerciallyavailable device, for comparison: Op amp flatband noise = 8nV/ 1/f corner frequency = 100 Hz AV = 2000 Measurement time = 100 sec Bandwidth = 2 Hz This example will result in about 2.2 mVPP (1.9 LSB) of output noise contribution due to the op amp alone, compared to about 594 μVPP (less than 0.5 LSB) when that op amp is replaced with the LMP201X which has no 1/f contribution. If the measurement time is increased from 100 seconds to 1 hour, the improvement realized by using the LMP201X would be a factor of about 4.8 times (2.86 mVPP compared to 596 μV when LMP201X is used) mainly because the LMP201X accuracy is not compromised by increasing the observation time. D) Copper leadframe construction minimizes any thermocouple effects which would degrade low level/high gain 12 In terms of the measured output peak-to-peak noise, the following relationship holds between output noise voltage, en pp, for different closed-loop gain, AV, settings, where −3 dB Bandwidth is BW: (1) 20071520 FIGURE 6. Composite Amplifier Configuration www.national.com LMP2011 Single/LMP2012 Dual data conversion application accuracy (see discussion under "The Benefits of the LMP201X" section above). E) Rail-to-Rail output swing maximizes the ADC dynamic range in 5-Volt single-supply converter applications. Below are some typical block diagrams showing the LMP201X used as an ADC amplifier (Figure 7 and Figure 8). 20071522 FIGURE 8. DC Coupled ADC Driver 13 www.national.com LMP2011 Single/LMP2012 Dual Physical Dimensions inches (millimeters) unless otherwise noted 5-Pin SOT23 NS Package Number MF0A5 8-Pin MSOP NS Package Number MUA08A www.national.com 14 LMP2011 Single/LMP2012 Dual 8-Pin SOIC NS Package Number M08A 15 www.national.com LMP2011 Single/LMP2012 Dual High Precision, Rail-to-Rail Output Operational Amplifier Notes For more National Semiconductor product information and proven design tools, visit the following Web sites at: Products Amplifiers Audio Clock Conditioners Data Converters Displays Ethernet Interface LVDS Power Management Switching Regulators LDOs LED Lighting PowerWise Serial Digital Interface (SDI) Temperature Sensors Wireless (PLL/VCO) www.national.com/amplifiers www.national.com/audio www.national.com/timing www.national.com/adc www.national.com/displays www.national.com/ethernet www.national.com/interface www.national.com/lvds www.national.com/power www.national.com/switchers www.national.com/ldo www.national.com/led www.national.com/powerwise www.national.com/sdi www.national.com/tempsensors www.national.com/wireless WEBENCH Analog University App Notes Distributors Green Compliance Packaging Design Support www.national.com/webench www.national.com/AU www.national.com/appnotes www.national.com/contacts www.national.com/quality/green www.national.com/packaging www.national.com/quality www.national.com/refdesigns www.national.com/feedback Quality and Reliability Reference Designs Feedback THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION (“NATIONAL”) PRODUCTS. NATIONAL MAKES NO REPRESENTATIONS OR WARRANTIES WITH RESPECT TO THE ACCURACY OR COMPLETENESS OF THE CONTENTS OF THIS PUBLICATION AND RESERVES THE RIGHT TO MAKE CHANGES TO SPECIFICATIONS AND PRODUCT DESCRIPTIONS AT ANY TIME WITHOUT NOTICE. NO LICENSE, WHETHER EXPRESS, IMPLIED, ARISING BY ESTOPPEL OR OTHERWISE, TO ANY INTELLECTUAL PROPERTY RIGHTS IS GRANTED BY THIS DOCUMENT. TESTING AND OTHER QUALITY CONTROLS ARE USED TO THE EXTENT NATIONAL DEEMS NECESSARY TO SUPPORT NATIONAL’S PRODUCT WARRANTY. EXCEPT WHERE MANDATED BY GOVERNMENT REQUIREMENTS, TESTING OF ALL PARAMETERS OF EACH PRODUCT IS NOT NECESSARILY PERFORMED. NATIONAL ASSUMES NO LIABILITY FOR APPLICATIONS ASSISTANCE OR BUYER PRODUCT DESIGN. BUYERS ARE RESPONSIBLE FOR THEIR PRODUCTS AND APPLICATIONS USING NATIONAL COMPONENTS. PRIOR TO USING OR DISTRIBUTING ANY PRODUCTS THAT INCLUDE NATIONAL COMPONENTS, BUYERS SHOULD PROVIDE ADEQUATE DESIGN, TESTING AND OPERATING SAFEGUARDS. EXCEPT AS PROVIDED IN NATIONAL’S TERMS AND CONDITIONS OF SALE FOR SUCH PRODUCTS, NATIONAL ASSUMES NO LIABILITY WHATSOEVER, AND NATIONAL DISCLAIMS ANY EXPRESS OR IMPLIED WARRANTY RELATING TO THE SALE AND/OR USE OF NATIONAL PRODUCTS INCLUDING LIABILITY OR WARRANTIES RELATING TO FITNESS FOR A PARTICULAR PURPOSE, MERCHANTABILITY, OR INFRINGEMENT OF ANY PATENT, COPYRIGHT OR OTHER INTELLECTUAL PROPERTY RIGHT. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS PRIOR WRITTEN APPROVAL OF THE CHIEF EXECUTIVE OFFICER AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: Life support devices or systems are devices which (a) are intended for surgical implant into the body, or (b) support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected to result in a significant injury to the user. A critical component is any component in a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system or to affect its safety or effectiveness. National Semiconductor and the National Semiconductor logo are registered trademarks of National Semiconductor Corporation. All other brand or product names may be trademarks or registered trademarks of their respective holders. Copyright© 2008 National Semiconductor Corporation For the most current product information visit us at www.national.com National Semiconductor Americas Technical Support Center Email: support@nsc.com Tel: 1-800-272-9959 www.national.com National Semiconductor Europe Technical Support Center Email: europe.support@nsc.com German Tel: +49 (0) 180 5010 771 English Tel: +44 (0) 870 850 4288 National Semiconductor Asia Pacific Technical Support Center Email: ap.support@nsc.com National Semiconductor Japan Technical Support Center Email: jpn.feedback@nsc.com